250ksps, +3V, 8-/4-Channel, 12-Bit ADCs with +2.5V Reference and Parallel Interface

Transcription

1 9-279; Rev ; 4/3 25ksps, +3V, 8-/4-Channel, 2-Bit ADCs General Description The low-power, 2-bit analog-todigital converters (ADCs) feature a successive-approximation ADC, automatic power-down, fast wake-up (2µs), an on-chip clock, +2.5V internal reference, and a high-speed, byte-wide parallel interface. They operate with a single +3V analog supply and feature a VLOGIC pin that allows them to interface directly with a +.8V to +5.5V digital supply. Power consumption is only 5.7mW (VDD = VLOGIC) at the maximum sampling rate of 25ksps. Two softwareselectable power-down modes enable the MAX26/ MAX263 to be shut down between conversions; accessing the parallel interface returns them to normal operation. Powering down between conversions can cut supply current to under µa at reduced sampling rates. Both devices offer software-configurable analog inputs for unipolar/bipolar and single-ended/pseudo-differential operation. In single-ended mode, the MAX26 has eight input channels and the MAX263 has four input channels (four and two input channels, respectively, when in pseudo-differential mode). Excellent dynamic performance and low power, combined with ease of use and small package size, make these converters ideal for battery-powered and dataacquisition applications or for other circuits with demanding power consumption and space requirements. The MAX26 is available in a 28-pin QSOP package, while the MAX263 is available in a 24-pin QSOP. For pin-compatible +5V, 2-bit versions, refer to the MAX262/MAX264 data sheet. Industrial Control Systems Energy Management Data-Acquisition Systems Applications Data Logging Patient Monitoring Touch Screens Ordering Information PART TEMP RANGE PIN-PACKAGE INL (LSB) MAX26ACEI C to +7 C 28 QSOP ±.5 MAX26BCEI C to +7 C 28 QSOP ± MAX26AEEI MAX26BEEI -4 C to +85 C 28 QSOP ±.5-4 C to +85 C 28 QSOP ± Ordering Information continued at end of data sheet. Features 2-Bit Resolution, ±.5 LSB Linearity +3V Single Operation User-Adjustable Logic Level (+.8V to +3.6V) Internal +2.5V Reference Software-Configurable, Analog Input Multiplexer 8-Channel Single Ended/ 4-Channel Pseudo-Differential (MAX26) 4-Channel Single Ended/ 2-Channel Pseudo-Differential (MAX263) Software-Configurable, Unipolar/Bipolar Inputs Low Power.9mA (25ksps).mA (ksps) 4µA (ksps) 2µA (Shutdown) Internal 3MHz Full-Power Bandwidth Track/Hold Byte-Wide Parallel (8 + 4) Interface Small Footprint 28-Pin QSOP (MAX26) 24-Pin QSOP (MAX263) TOP VIEW HBEN D7 2 D6 3 D5 4 D4 5 D3/D 6 D2/D 7 D/D9 8 D/D8 9 INT RD 2 CLK 3 Pin Configurations MAX26 CS 4 5 CH7 QSOP 28 V LOGIC 27 V DD 26 REF 25 REFADJ 24 GND CH 2 CH 2 CH2 9 CH3 8 CH4 7 CH5 6 CH6 Pin Configurations continued at end of data sheet. Typical Operating Circuits appear at end of data sheet. Maxim Integrated Products For pricing, delivery, and ordering information, please contact Maxim/Dallas Direct! at , or visit Maxim s website at

2 25ksps, +3V, 8-/4-Channel, 2-Bit ADCs ABSOLUTE MAXIMUM RATINGS V DD to GND...-.3V to +6V V LOGIC to GND...-.3V to +6V CH CH7, to GND...-.3V to (V DD +.3V) REF, REFADJ to GND...-.3V to (V DD +.3V) Digital Inputs to GND...-.3V to +6V Digital Outputs (D D, INT) to GND...-.3V to (V LOGIC +.3V) Stresses beyond those listed under Absolute Maximum Ratings may cause permanent damage to the device. These are stress ratings only, and functional operation of the device at these or any other conditions beyond those indicated in the operational sections of the specifications is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability. ELECTRICAL CHARACTERISTICS Continuous Power Dissipation (T A = +7 C) 24-Pin QSOP (derate 9.5mW/ C above +7 C)...762mW 28-Pin QSOP (derate 8.mW/ C above +7 C)...667mW Operating Temperature Ranges MAX26_C /MAX263_C... C to +7 C MAX26_E /MAX263_E...-4 C to +85 C Storage Temperature Range C to +5 C Lead Temperature (soldering, s)...+3 C (V DD = V LOGIC = +2.7V to +3.6V, = GND, REFADJ = V DD, V REF = +2.5V, 4.7µF capacitor at REF pin, f CLK = 4.8MHz (5% duty cycle); T A = T MIN to T MAX, unless otherwise noted. Typical values are at T A = +25 C.) PARAMETER DC ACCURACY (Note ) Resolution Relative Accuracy (Note 2) Differential Nonlinearity Offset Error Gain Error Gain Temperature Coefficient SYMBOL RES INL DNL MAX26_A MAX26_B No missing codes overtemperature (Note 3) CONDITIONS MIN TYP MAX 2 ±2. ±.5 ± ± ±4 ±4 UNITS Bits LSB LSB LSB LSB ppm/ C Channel-to-Channel Offset Matching ±.2 LSB DYNAMIC SPECIFICATIONS (f IN(sine wave) = 5kHz, V IN = 2.5V P-P, 25ksps, external f CLK = 4.8MHz, bipolar input mode) Signal-to-Noise Plus Distortion SINAD 67 7 db Total Harmonic Distortion (Including 5th-Order Harmonic) THD -78 db Spurious-Free Dynamic Range SFDR 8 db Intermodulation Distortion IMD f IN = 49kHz, f IN2 = 52kHz 76 db Channel-to-Channel Crosstalk f IN = 25kHz, V IN = 2.5V P-P (Note 4) -78 db Full-Linear Bandwidth SINAD > 68dB 25 khz Full-Power Bandwidth -3dB rolloff 3 MHz CONVERSION RATE External clock mode 3.3 Conversion Time (Note 5) t CONV External acquisition/internal clock mode µs Internal acquisition/internal clock mode Track/Hold Acquisition Time t ACQ 625 ns Aperture Delay External acquisition or external clock mode 5 ns Aperture Jitter External acquisition or external clock mode Internal acquisition/internal clock mode <5 <2 ps External Clock Frequency f CLK. 4.8 MHz Duty Cycle 3 7 % 2

3 25ksps, +3V, 8-/4-Channel, 2-Bit ADCs ELECTRICAL CHARACTERISTICS (continued) (V DD = V LOGIC = +2.7V to +3.6V, = GND, REFADJ = V DD, V REF = +2.5V, 4.7µF capacitor at REF pin, f CLK = 4.8MHz (5% duty cycle); T A = T MIN to T MAX unless otherwise noted. Typical values are at T A = +25 C.) PARAMETER ANALOG INPUTS Analog Input Voltage Range, Single Ended and Differential (Note 6) Multiplexer Leakage Current Input Capacitance INTERNAL REFERENCE REF Output Voltage REF Short-Circuit Current REF Temperature Coefficient REFADJ Input Range REFADJ High Threshold Load Regulation Capacitive Bypass at REFADJ Capacitive Bypass at REF EXTERNAL REFERENCE AT REF SYMBOL V IN C IN TC REF Unipolar, V = CONDITIONS On-/off-leakage current, V IN = or V DD T A = C to +7 C For small adjustments To power down the internal reference to.5ma output load (Note 7) MIN TYP MAX V REF Bipolar, V = V REF / 2 -V REF /2 +V REF /2 ±. ± 2 UNITS µa pf V 5 ma ±2 ppm/ C ± mv V DD -. V.2 mv/ma. µf 4.7 µf V REF Input Voltage Range V REF. V DD + 5mV V REF Input Current I REF DIGITAL INPUTS AND OUTPUTS Input High Voltage V IH Input Low Voltage V IL Input Hysteresis V HYS Input Leakage Current I IN Input Capacitance C IN Output Low Voltage V OL Output High Voltage V OH Tri-State Leakage Current I LEAKAGE Tri-State Output Capacitance C OUT V REF = 2.5V, f SAMPLE = 25ksps 2 3 Shutdown mode 2 V LOGIC = 2.7V 2. V LOGIC =.8V.5 V LOGIC = 2.7V.8 V LOGIC =.8V.5 2 V IN = or V DD ±. ± 5 I SINK =.6mA.4 I SOURCE = ma V LOGIC -.5 CS = V DD ±. ± CS = V DD 5 µa V V mv µa pf V V µa pf 3

4 25ksps, +3V, 8-/4-Channel, 2-Bit ADCs ELECTRICAL CHARACTERISTICS (continued) (V DD = V LOGIC = +2.7V to +3.6V, = GND, REFADJ = V DD, V REF = +2.5V, 4.7µF capacitor at REF pin, f CLK = 4.8MHz (5% duty cycle); T A = T MIN to T MAX unless otherwise noted. Typical values are at T A = +25 C.) PARAMETER SYMBOL CONDITIONS MIN TYP MAX UNITS POWER REQUIREMENTS Analog Supply Voltage V DD V Digital Supply Voltage V LOGIC.8 V DD +.3 V Operating mode, Internal reference Positive Supply Current I DD f SAMPLE = 25ksps External reference ma Internal reference.9.2 Standby mode External reference.5.8 Shutdown mode 2 µa V LOGIC Current I LOGIC C L = 2pF f SAMPLE = 25ksps 5 Not converting 2 µa Power-Supply Rejection PSR V DD = 3V ±%, full-scale input ±.4 ±.9 mv TIMING CHARACTERISTICS (V DD = V LOGIC = +2.7V to +3.6V, = GND, REFADJ = V DD, V REF = +2.5V, 4.7µF capacitor at REF pin, f CLK = 4.8MHz (5% duty cycle); T A = T MIN to T MAX, unless otherwise noted. Typical values are at T A = +25 C.) PARAMETER SYMBOL CONDITIONS MIN TYP MAX UNITS CLK Period t CP 28 ns CLK Pulse Width High t CH 4 ns CLK Pulse Width Low t CL 4 ns Data Valid to Rise Time t DS 4 ns Rise to Data Valid Hold Time t DH ns to CLK Fall Setup Time t CWS 4 ns CLK Fall to Hold Time t CWH 4 ns CS to CLK or Setup Time CLK or to CS Hold Time t CSWS 6 ns t CSWH ns CS Pulse Width t CS ns Pulse Width t (Note 8) 6 ns CS Rise to Output Disable t TC C LOAD = 2pF (Figure ) 2 ns 4

5 25ksps, +3V, 8-/4-Channel, 2-Bit ADCs TIMING CHARACTERISTICS (continued) (V DD = V LOGIC = +2.7V to +3.6V, = GND, REFADJ = V DD, V REF = +2.5V, 4.7µF capacitor at REF pin, f CLK = 4.8MHz (5% duty cycle); T A = T MIN to T MAX, unless otherwise noted. Typical values are at T A = +25 C.) PARAMETER SYMBOL CONDITIONS MIN TYP MAX UNITS RD Rise to Output Disable t TR C LOAD = 2pF, Figure 2 7 ns RD Fall to Output Data Valid t DO C LOAD = 2pF, Figure 2 7 ns HBEN to Output Data Valid t DO C LOAD = 2pF, Figure 2 ns RD Fall to INT High Delay t INT C LOAD = 2pF, Figure ns CS Fall to Output Data Valid t DO2 C LOAD = 2pF, Figure ns Note : Tested at V DD = +3V, = GND, unipolar single-ended input mode. Note 2: Relative accuracy is the deviation of the analog value at any code from its theoretical value after offset and gain errors have been removed. Note 3: Offset nulled. Note 4: On channel is grounded; sine wave applied to off channels. Note 5: Conversion time is defined as the number of clock cycles times the clock period; clock has 5% duty cycle. Note 6: Input voltage range referenced to negative input. The absolute range for the analog inputs is from GND to V DD. Note 7: External load should not change during conversion for specified accuracy. Note 8: When bit 5 is set low for internal acquisition, must not return low until after the first falling clock edge of the conversion. V LOGIC 3kΩ DOUT 3kΩ C LOAD 2pF DOUT C LOAD 2pF a) HIGH-Z TO V OH AND V OL TO V OH b) HIGH-Z TO V OL AND V OH TO V OL Figure. Load Circuits for Enable/Disable Times 5

6 25ksps, +3V, 8-/4-Channel, 2-Bit ADCs Typical Operating Characteristics (V DD = V LOGIC = +3V, V REF = +2.5V, f CLK = 4.8MHz, C L = 2pF, T A = +25 C, unless otherwise noted.) INL (LSB) INTEGRAL NONLINEARITY vs. DIGITAL OUTPUT CODE DIGITAL OUTPUT CODE MAX26/63 toc DNL (LSB) DIFFERENTIAL NONLINEARITY vs. DIGITAL OUTPUT CODE DIGITAL OUTPUT CODE MAX26/63 toc2, IDD (µa) SUPPLY CURRENT vs. SAMPLE FREQUENCY WITH INTERNAL REFERENCE WITH EXTERNAL REFERENCE. k k k M f SAMPLE (Hz) MAX26/63 toc SUPPLY CURRENT vs. SUPPLY VOLTAGE R L = CODE = MAX26/63 toc SUPPLY CURRENT vs. TEMPERATURE R L = CODE = MAX26/63 toc STANDBY CURRENT vs. SUPPLY VOLTAGE MAX26/63 toc6 IDD (ma) IDD (ma) STANDBY IDD (µa) V DD (V) TEMPERATURE ( C) V DD (V) STANDBY IDD (µa) STANDBY CURRENT vs. TEMPERATURE MAX26/63 toc7 POWER-DOWN IDD (µa) POWER-DOWN CURRENT vs. SUPPLY VOLTAGE MAX26/63 toc8 POWER-DOWN IDD (µa) POWER-DOWN CURRENT vs. TEMPERATURE MAX26/63 toc TEMPERATURE ( C) V DD (V) TEMPERATURE ( C) 6

7 25ksps, +3V, 8-/4-Channel, 2-Bit ADCs Typical Operating Characteristics (continued) (V DD = V LOGIC = +3V, V REF = +2.5V, f CLK = 4.8MHz, C L = 2pF, T A = +25 C, unless otherwise noted.) VREF (V) INTERNAL REFERENCE VOLTAGE vs. SUPPLY VOLTAGE V DD (V) MAX26/63 toc VREF (V) INTERNAL REFERENCE VOLTAGE vs. TEMPERATURE TEMPERATURE ( C) MAX26/63 toc OFFSET ERROR (LSB) OFFSET ERROR vs. SUPPLY VOLTAGE V DD (V) MAX26/63 toc2 OFFSET ERROR (LSB) OFFSET ERROR vs. TEMPERATURE MAX26/63 toc3 GAIN ERROR (LSB) - GAIN ERROR vs. SUPPLY VOLTAGE MAX26/63 toc4 GAIN ERROR (LSB) GAIN ERROR vs. TEMPERATURE MAX26/63 toc TEMPERATURE ( C) V DD (V) TEMPERATURE ( C) 25 2 LOGIC SUPPLY CURRENT vs. SUPPLY VOLTAGE MAX26/63 toc LOGIC SUPPLY CURRENT vs. TEMPERATURE MAX26/63 toc7 2-2 FFT PLOT V DD = 3V f IN = 5kHz f SAMPLE = 25ksps MAX26/63 toc8 ILOGIC (µa) 5 ILOGIC (µa) 5 AMPLITUDE (db) V DD (V) TEMPERATURE ( C) FREQUENCY (khz) 7

8 25ksps, +3V, 8-/4-Channel, 2-Bit ADCs PIN MAX26 MAX NAME HBEN D7 D6 D5 D4 D3/D D2/D D/D9 D/D8 INT FUNCTION High Byte Enable. Used to multiplex the 2-bit conversion result: : Four MSBs are multiplexed on the data bus. : Eight LSBs are available on the data bus. Tri-State Digital I/O Line (D7) Tri-State Digital I/O Line (D6) Tri-State Digital I/O Line (D5) Tri-State Digital I/O Line (D4) Tri-State Digital I/O Line (D3, HBEN = ; D, HBEN = ) Tri-State Digital I/O Line (D2, HBEN = ; D, HBEN = ) Tri-State Digital I/O Line (D, HBEN = ; D9, HBEN = ) Tri-State Digital I/O Line (D, HBEN = ; D8, HBEN = ) INT goes low when the conversion is complete and the output data is ready. Pin Description RD Active-Low Read Select. If CS is low, a falling edge on RD enables the read operation on the data bus. 2 2 Active-Low Write Select. When CS is low in internal acquisition mode, a rising edge on latches in configuration data and starts an acquisition plus a conversion cycle. When CS is low in external acquisition mode, the first rising edge on ends acquisition and starts a conversion. 3 3 CLK Clock Input. In external clock mode, drive CLK with a TTL-/CMOS-compatible clock. In internal clock mode, connect this pin to either V DD or GND CS CH7 CH6 CH5 CH4 CH3 CH2 CH CH Active-Low Chip Select. When CS is high, digital outputs (D7 D) are high impedance. Analog Input Channel 7 Analog Input Channel 6 Analog Input Channel 5 Analog Input Channel 4 Analog Input Channel 3 Analog Input Channel 2 Analog Input Channel Analog Input Channel 23 9 Ground Reference for Analog Inputs. Sets zero-code voltage in single-ended mode and must be stable to ±.5 LSB during conversion GND Analog and Digital Ground 25 2 REFADJ Bandgap Reference Output/Bandgap Reference Buffer Input. Bypass to GND with a.µf capacitor. When using an external reference, connect REFADJ to V DD to disable the internal bandgap reference REF Bandgap Reference Buffer Output/External Reference Input. Add a 4.7µF capacitor to GND when using the internal reference V DD Analog +5V Power Supply. Bypass with a.µf capacitor to GND V LOGIC Digital Power Supply. V LOGIC powers the digital outputs of the data converter and can range from +.8V to (V DD + 3mV). 8

9 25ksps, +3V, 8-/4-Channel, 2-Bit ADCs Detailed Description Converter Operation The ADCs use a successiveapproximation (SAR) conversion technique and an input track/hold (T/H) stage to convert an analog input signal to a 2-bit digital output. Their parallel (8 + 4) output format provides an easy interface to standard microprocessors (µps). Figure 2 shows the simplified internal architecture of the. Single-Ended and Pseudo-Differential Operation The sampling architecture of the ADC s analog comparator is illustrated in the equivalent input circuit in Figure 3. In single-ended mode, IN+ is internally switched to channels CH CH7 for the MAX26 (Figure 3a) and to CH CH3 for the MAX263 (Figure 3b), while IN- is switched to (Table 3). In differential mode, IN+ and IN- are selected from analog input pairs (Table 4) and are internally switched to either of the analog inputs. This configuration is pseudodifferential in that only the signal at IN+ is sampled. The return side (IN-) must remain stable within ±.5 LSB (±. LSB for best performance) with respect to GND during a conversion. To accomplish this, connect a.µf capacitor from IN- (the selected input) to GND. During the acquisition interval, the channel selected as the positive input (IN+) charges capacitor C HOLD. At the end of the acquisition interval, the T/H switch opens, retaining charge on C HOLD as a sample of the signal at IN+. The conversion interval begins with the input multiplexer switching CHOLD from the positive input (IN+) to the negative input (IN-). This unbalances node zero at the comparator s positive input. The capacitive digital-toanalog converter (DAC) adjusts during the remainder of the conversion cycle to restore node to V within the limits of 2-bit resolution. This action is equivalent to transferring a 2pF[(V IN+ ) - (V IN- )] charge from C HOLD to the binary-weighted capacitive DAC, which in turn forms a digital representation of the analog input signal. REF REFADJ (CH7) (CH6) A V = 2.5 7kΩ.22V REFERENCE (CH5) (CH4) CH3 CH2 CH ANALOG INPUT MULTIPLEXER T/H CHARGE REDISTRIBUTION 2-BIT DAC P CH 2 CLK CLOCK SUCCESSIVE- APPROXIMATION REGISTER CS RD INT CONTROL LOGIC AND LATCHES MUX MAX26 MAX263 HBEN 8 8 V DD TRI-STATE, BIDIRECTIONAL I/O INTERFACE V LOGIC GND ( ) ARE FOR MAX26 ONLY. D D7 8-BIT DATA BUS Figure 2. Simplified Internal Architecture for 8-/4-Channel 9

10 25ksps, +3V, 8-/4-Channel, 2-Bit ADCs CH CH CH2 CH3 CH4 CH5 CH6 CH7 REF INPUT MUX 2-BIT CAPACITIVE DAC C HOLD + 2pF C SWITCH TRACK T/H SWITCH R IN 8Ω ZERO HOLD PARATOR SINGLE-ENDED MODE: IN+ = CH CH7, IN- = PSEUDO-DIFFERENTIAL MODE: IN+ AND IN- SELECTED FROM PAIRS CH/CH, CH2/CH3, CH4/CH5, AND CH6/CH7 Figure 3a. MAX26 Simplified Input Structure CH CH CH2 CH3 REF INPUT MUX 2-BIT CAPACITIVE DAC C HOLD + 2pF C SWITCH TRACK T/H SWITCH R IN 8Ω ZERO HOLD AT THE SAMPLING INSTANT, THE MUX INPUT SWITCHES FROM THE SELECTED IN+ CHANNEL TO THE SELECTED IN- CHANNEL. PARATOR SINGLE-ENDED MODE: IN+ = CH CH3, IN- = PSEUDO-DIFFERENTIAL MODE: IN+ AND IN- SELECTED FROM PAIRS CH/CH AND CH2/CH3 Figure 3b. MAX263 Simplified Input Structure AT THE SAMPLING INSTANT, THE MUX INPUT SWITCHES FROM THE SELECTED IN+ CHANNEL TO THE SELECTED IN- CHANNEL. Analog Input Protection Internal protection diodes, which clamp the analog input to V DD and GND, allow each input channel to swing within (GND - 3mV) to (V DD + 3mV) without damage. However, for accurate conversions near full scale, both inputs must not exceed (V DD + 5mV) or be less than (GND - 5mV). If an off-channel analog input voltage exceeds the supplies by more than 5mV, limit the forward-bias input current to 4mA. Track/Hold The T/H stage enters its tracking mode on the rising edge of. In external acquisition mode, the part enters its hold mode on the next rising edge of. In internal acquisition mode, the part enters its hold mode on the fourth falling edge of clock after writing the control byte. Note that, in internal clock mode, this occurs approximately µs after writing the control byte. In single-ended operation, IN- is connected to and the converter samples the positive (+) input. In pseudo-differential operation, IN- connects to the negative (-) input, and the difference of (IN+) - (IN-) is sampled. At the beginning of the next conversion, the positive input connects back to IN+ and C HOLD charges to the input signal. The time required for the T/H stage to acquire an input signal depends on how quickly its input capacitance is charged. If the input signal s source impedance is high, the acquisition time lengthens, and more time must be allowed between conversions. The acquisition time, t ACQ, is the maximum time the device takes to acquire the signal and is also the minimum time required for the signal to be acquired. Calculate this with the following equation: t ACQ = 9(R S + R IN )C IN where R S is the source impedance of the input signal, R IN (8Ω) is the input resistance, and C IN (2pF) is the ADC s input capacitance. Source impedances below 3kΩ have no significant impact on the MAX26/ MAX263s AC performance. Higher source impedances can be used if a.µf capacitor is connected to the individual analog inputs. Together with the input impedance, this capacitor forms an RC filter, limiting the ADC s signal bandwidth. Input Bandwidth The T/H stage offers a 25kHz fulllinear and a 3MHz full-power bandwidth, enabling these parts to use undersampling techniques to digitize high-speed transients and measure periodic signals with bandwidths exceeding the ADC s sampling rate. To avoid high-frequency signals being aliased into the frequency band of interest, anti-alias filtering is recommended. Starting a Conversion Initiate a conversion by writing a control byte that selects the multiplexer channel and configures the for either unipolar or bipolar operation. A write pulse ( + CS) can either start an acquisition interval or initiate a combined acquisition plus

11 25ksps, +3V, 8-/4-Channel, 2-Bit ADCs conversion. The sampling interval occurs at the end of the acquisition interval. The ACQMOD (acquisition mode) bit in the input control byte (Table ) offers two options for acquiring the signal: an internal and an external acquisition. The conversion period lasts for 3 clock cycles in either the internal or external clock or acquisition mode. Writing a new control byte during a conversion cycle aborts the conversion and starts a new acquisition interval. Internal Acquisition Select internal acquisition by writing the control byte with the ACQMOD bit cleared (ACQMOD = ). This causes the write pulse to initiate an acquisition interval whose duration is internally timed. Conversion starts when this acquisition interval ends (three external cycles or approximately µs in internal clock mode) (Figure 4). Note that, when the internal acquisition is combined with the internal clock, the aperture jitter can be as high as 2ps. Internal clock users wishing to achieve the 5ps jitter specification should always use external acquisition mode. External Acquisition Use external acquisition mode for precise control of the sampling aperture and/or dependent control of acquisition and conversion times. The user controls acquisition and start-of-conversion with two separate write pulses. The first pulse, written with ACQMOD =, starts an acquisition interval of indeterminate length. The second write pulse, written with ACQMOD =, terminates acquisition and starts conversion on s rising edge (Figure 5). The address bits for the input multiplexer must have the same values on the first and second write pulse. Power-down mode bits (PD, PD) can assume new values on the second write pulse (see the Power-Down Modes section). Changing other bits in the control byte corrupts the conversion. Reading a Conversion A standard interrupt signal, INT, is provided to allow the to flag the µp when the conversion has ended and a valid result is available. INT goes low when the conversion is complete and the output data is ready (Figures 4 and 5). It returns high on the first read cycle or if a new control byte is written. Table. Control Byte Functional Description BIT NAME FUNCTION PD and PD select the various clock and power-down modes. Full power-down mode. Clock mode is unaffected. D7, D6 PD, PD Standby power-down mode. Clock mode is unaffected. Normal operation mode. Internal clock mode selected. Normal operation mode. External clock mode selected. D5 D4 D3 D2, D, D ACQMOD SGL/DIF UNI/BIP A2, A, A ACQMOD = : Internal acquisition mode ACQMOD = : External acquisition mode SGL/DIF = : Pseudo-differential analog input mode SGL/DIF = : Single-ended analog input mode In single-ended mode, input signals are referred to. In pseudo-differential mode, the voltage difference between two channels is measured (Tables 2 and 3). UNI/BIP = : Bipolar mode UNI/BIP = : Unipolar mode In unipolar mode, an analog input signal from to V REF can be converted; in bipolar mode, the signal can range from -V REF /2 to +V REF /2. Address bits A2, A, A select which of the 8/4 () channels are to be converted (Tables 3 and 4).

12 25ksps, +3V, 8-/4-Channel, 2-Bit ADCs CS D7 D INT RD HBEN t CS t ACQ t CONV t CSWS t t CSWH t DS CONTROL BYTE ACQMOD = t DH t INT t D t D t TR DOUT HIGH-Z HIGH/LOW BYTE VALID HIGH/LOW BYTE VALID HIGH-Z Figure 4. Conversion Timing Using Internal Acquisition Mode t CS CS t CSWS t ACQ t CONV t t CSHW t DS t DH D7 D CONTROL BYTE ACQMOD = CONTROL BYTE ACQMOD = t INT INT RD HBEN t D t D t TR DOUT HIGH-Z HIGH/LOW BYTE VALID HIGH/LOW BYTE VALID HIGH-Z Figure 5. Conversion Timing Using External Acquisition Mode 2

13 25ksps, +3V, 8-/4-Channel, 2-Bit ADCs Selecting Clock Mode The operate with either an internal or an external clock. Control bits D6 and D7 select either internal or external clock mode. The parts retain the last-requested clock mode if a power-down mode is selected in the current input word. For both internal and external clock mode, internal or external acquisition can be used. At power-up, the enter the default external clock mode. Internal Clock Mode Select internal clock mode to release the µp from the burden of running the SAR conversion clock. To select this mode, bit D7 of the control byte must be set to and bit D6 must be set to zero. The internal clock frequency is then selected, resulting in a conversion time of 3.6µs. When using the internal clock mode, tie the CLK pin either high or low to prevent the pin from floating. External Clock Mode To select the external clock mode, bits D6 and D7 of the control byte must be set to. Figure 6 shows the clock and timing relationship for internal (Figure 6a) and external (Figure 6b) acquisition modes with an external clock. For proper operation, a khz to 4.8MHz clock frequency with 3% to 7% duty cycle is recommended. Operating the with clock frequencies lower than khz is not recommended, because it causes a voltage droop across the hold capacitor in the T/H stage that results in degraded performance. Digital Interface Input (control byte) and output data are multiplexed on a tri-state parallel interface. This parallel interface (I/O) can easily be interfaced with standard µps. Signals CS,, and RD control the write and read operations. CS represents the chip-select signal, which enables a µp to address the as an I/O port. When high, CS disables the CLK,, and RD inputs and forces the interface into a high-impedance (high-z) state. Input Format The control byte is latched into the device on pins D7 D during a write command. Table 2 shows the control byte format. Output Format The output format for both the is binary in unipolar mode and two s complement in bipolar mode. When reading the output data, CS and RD must be low. When HBEN =, the lower 8 bits are read. With HBEN =, the upper 4 bits are available and the output data bits D7 D4 are set either low in unipolar mode or set to the value of the MSB in bipolar mode (Table 5). ACQUISITION STARTS t CP ACQUISITION ENDS CONVERSION STARTS CLK t CWS t CH t CL ACQMOD = GOES HIGH WHEN CLK IS HIGH. t CWH ACQUISITION STARTS ACQUISITION ENDS CONVERSION STARTS CLK ACQMOD = GOES HIGH WHEN CLK IS LOW. Figure 6a. External Clock and Timing (Internal Acquisition Mode) 3

14 25ksps, +3V, 8-/4-Channel, 2-Bit ADCs CLK CLK ACQUISITION STARTS ACQUISITION ENDS t DH t CWS ACQMOD = GOES HIGH WHEN CLK IS HIGH. ACQMOD = ACQUISITION STARTS ACQUISITION ENDS t DH t CWH ACQMOD = GOES HIGH WHEN CLK IS LOW. ACQMOD = CONVERSION STARTS CONVERSION STARTS Figure 6b. External Clock and Timing (External Acquisition Mode) Table 2. Control Byte Format D7 (MSB) D6 D5 D4 D3 D2 D D (LSB) PD PD ACQMOD SGL/DIF UNI/BIP A2 A A Table 3. Channel Selection for Single-Ended Operation (SGL/DIF = ) A2 A A CH + CH + CH2 + CH3 CH4* CH5* CH6* CH7* *Channels CH4 CH7 apply to MAX26 only. 4

15 25ksps, +3V, 8-/4-Channel, 2-Bit ADCs Table 4. Channel Selection for Pseudo-Differential Operation (SGL/DIF = ) A2 A A CH *Channels CH4 CH7 apply to MAX26 only. CH + CH2 + - CH3 - + CH4* CH5* Applications Information Power-On Reset When power is first applied, internal power-on reset circuitry activates the in external clock mode and sets INT high. After the power supplies stabilize, the internal reset time is µs, and no conversions should be attempted during this phase. When using the internal reference, 5µs is required for V REF to stabilize. Internal and External Reference The can be used with an internal or external reference voltage. An external reference can be connected directly to REF or REFADJ. An internal buffer is designed to provide +2.5V at REF for both the MAX26 and the MAX263. The internally trimmed +.22V reference is buffered with a +2.5V/V gain. Table 5. Data-Bus Output (8 + 4 Parallel Interface) +3V CH6* CH7* Internal Reference With the internal reference, the full-scale range is +2.5V with unipolar inputs and ±.25V with bipolar inputs. The internal reference buffer allows for small adjustments (±mv) in the reference voltage (Figure 7). Note that the reference buffer must be compensated with an external capacitor (4.7µF min) connected between REF and GND to reduce reference noise and switching spikes from the ADC. To further minimize noise on the reference, connect a.µf capacitor between REFADJ and GND. External Reference With both the MAX26 and MAX263, an external reference can be placed at either the input (REFADJ) or the output (REF) of the internal reference buffer amplifier. Using the REFADJ input makes buffering the external reference unnecessary. The REFADJ input impedance is typically 7kΩ. PIN D D D2 D3 D4 D5 D6 D7 HBEN = HBEN = BIT (LSB) BIT 8 BIT BIT 9 BIT 2 BIT BIT 3 BIT (MSB) BIPOLAR BIT 4 (UNI/BIP = ) BIT BIT 5 BIT BIT 6 BIT BIT 7 BIT UNIPOLAR (UNI/BIP = ) 5kΩ 5kΩ GND 33kΩ.µF GND 4.7µF MAX26 MAX263 REFADJ REF Figure 7. Reference Voltage Adjustment with External Potentiometer 5

16 25ksps, +3V, 8-/4-Channel, 2-Bit ADCs When applying an external reference to REF, disable the internal reference buffer by connecting REFADJ to VDD. The DC input resistance at REF is 25kΩ. Therefore, an external reference at REF must deliver up to 2µA DC load current during a conversion and have an output impedance less than Ω. If the reference has higher output impedance or is noisy, bypass it close to the REF pin with a 4.7µF capacitor. Power-Down Modes Save power by placing the converter in a low-current shutdown state between conversions. Select standby mode or shutdown mode using bits D6 and D7 of the control byte (Tables and 2). In both software powerdown modes, the parallel interface remains active, but the ADC does not convert. Standby Mode While in standby mode, the supply current is 85µA (typ). The part powers up on the next rising edge on and is ready to perform conversions. This quick turn-on time allows the user to realize significantly reduced power consumption for conversion rates below 25ksps. Shutdown Mode Shutdown mode turns off all chip functions that draw quiescent current, reducing the typical supply current to 2µA immediately after the current conversion is completed. A rising edge on causes the to exit shutdown mode and return to normal operation. To achieve full 2-bit accuracy with a 4.7µF reference bypass capacitor, 5µs is required after power-up. Waiting 5µs in standby mode, instead of in full-power mode, can reduce power consumption by a factor of 3 or more. When using an external reference, only 5µs is required after power-up. Enter standby mode by performing a dummy conversion with the control byte specifying standby mode. Note: Bypassing capacitors larger than 4.7µF between REF and GND results in longer power-up delays. Transfer Function Table 6 shows the full-scale voltage ranges for unipolar and bipolar modes. Figure 8 depicts the nominal, unipolar input/output (I/O) transfer function and Figure 9 shows the bipolar I/O transfer function. Code transitions occur halfway between successive-integer LSB values. Output coding is binary, with LSB = (V REF / 496). Maximum Sampling Rate/ Achieving 3ksps When running at the maximum clock frequency of 4.8MHz, the specified throughput of 25ksps is achieved by completing a conversion every 9 clock cycles: write cycle, 3 acquisition cycles, 3 conver- OUTPUT CODE... FS = REF +... ZS = FULL-SCALE TRANSITION OUTPUT CODE FS = REF 2 ZS = LSB = REF REF -FS = + 2 REF LSB = () 248 INPUT VOLTAGE (LSB) FS - 3 /2 LSB FS * V REF / 2 - FS * INPUT VOLTAGE (LSB) +FS - LSB Figure 8. Unipolar Transfer Function Figure 9. Bipolar Transfer Function 6

17 25ksps, +3V, 8-/4-Channel, 2-Bit ADCs Table 6. Full Scale and Zero Scale for Unipolar and Bipolar Operation Full scale Zero scale UNIPOLAR MODE V REF + sion cycles, and 2 read cycles. This assumes that the results of the last conversion are read before the next control byte is written. Throughputs up to 3ksps can be achieved by first writing a control word to begin the acquisition cycle of the next conversion, then reading the results of the previous conversion from the bus (Figure ). This technique allows a conversion to be completed every 6 clock cycles. Note that the switching of the data bus during acquisition or conversion can cause additional supply noise, which can make it difficult to achieve true 2-bit performance. Layout, Grounding, and Bypassing For best performance, use printed circuit (PC) boards. Wire-wrap configurations are not recommended since the layout should ensure proper separation of analog and digital traces. Do not run analog and digital lines parallel to each other, and do not lay out digital signal paths underneath the ADC package. Use separate analog and digital PC board ground sections with only one star point (Figure ) connecting the two ground systems (analog and digital). For lowest noise operation, ensure the ground return to the star ground s power supply is low impedance and as short as possible. Route digital signals far away from sensitive analog and reference inputs. High-frequency noise in the power supply (VDD) could influence the proper operation of the ADC s fast comparator. Bypass V DD to the star ground with a network of two parallel capacitors,.µf and 4.7µF, located as close as possible to the s powersupply pin. Minimize capacitor lead length for best supply-noise rejection; add an attenuation resistor (5Ω) if the power supply is extremely noisy. Positive full scale Zero scale BIPOLAR MODE V REF /2 + Negative full scale -V REF /2 + Definitions Integral Nonlinearity Integral nonlinearity (INL) is the deviation of the values on an actual transfer function from a straight line. This straight line can be either a best-straight-line fit or a line drawn between the end points of the transfer function, once offset and gain errors have been nullified. The static linearity parameters for the are measured using the end-point method. Differential Nonlinearity Differential nonlinearity (DNL) is the difference between an actual step width and the ideal value of LSB. A DNL error specification of less than LSB guarantees no missing codes and a monotonic transfer function. Aperture Definitions Aperture jitter (taj) is the sample-to-sample variation in the time between the samples. Aperture delay (t AD ) is the time between the rising edge of the sampling clock and the instant when an actual sample is taken. Signal-to-Noise Ratio For a waveform perfectly reconstructed from digital samples, signal-to-noise ratio (SNR) is the ratio of the full-scale analog input (RMS value) to the RMS quantization error (residual error). The ideal, theoretical minimum analog-to-digital noise is caused by quantization error only and results directly from the ADC s resolution (N bits): SNR = (6.2 x N +.76)dB In reality, there are other noise sources besides quantization noise: thermal noise, reference noise, clock jitter, etc. Therefore, SNR is computed by taking the ratio of the RMS signal to the RMS noise, which includes all spectral components minus the fundamental, the first five harmonics, and the DC offset. Signal-to-Noise Plus Distortion Signal-to-noise plus distortion (SINAD) is the ratio of the fundamental input frequency s RMS amplitude to the RMS equivalent of all other ADC output signals: SINAD (db) = 2 x log (SignalRMS / NoiseRMS) 7

18 25ksps, +3V, 8-/4-Channel, 2-Bit ADCs CLK RD HBEN D7 D STATE CONTROL BYTE D7 D LOW BYTE ACQUISITION D D8 HIGH BYTE CONTROL BYTE CONVERSION D7 D LOW BYTE D D8 HIGH BYTE ACQUISITION SAMPLING INSTANT Figure. Timing Diagram for Fastest Conversion Effective Number of Bits Effective number of bits (ENOB) indicates the global accuracy of an ADC at a specific input frequency and sampling rate. An ideal ADC error consists of quantization noise only. With an input range equal to the fullscale range of the ADC, calculate the effective number of bits as follows: ENOB = (SINAD -.76) / 6.2 Total Harmonic Distortion Total harmonic distortion (THD) is the ratio of the RMS sum of the first five harmonics of the input signal to the fundamental itself. This is expressed as: THD = x log V + V + V + V / V where V is the fundamental amplitude, and V 2 through V 5 are the amplitudes of the 2nd- through 5th-order harmonics. Spurious-Free Dynamic Range Spurious-free dynamic range (SFDR) is the ratio of the RMS amplitude of the fundamental (maximum signal component) to the RMS value of the next-largest distortion component. R* = 5Ω SUPPLIES +3V V LOGIC = +2V/+3V GND V DD *OPTIONAL 4.7µF.µF GND MAX26 MAX263 +2V/+3V DGND DIGITAL CIRCUITRY Figure. Power-Supply and Grounding Connections TRANSISTOR COUNT: 578 SUBSTRATE CONNECTED TO GND Chip Information 8

19 25ksps, +3V, 8-/4-Channel, 2-Bit ADCs µp CONTROL INPUTS CLK MAX26 CS V LOGIC V DD REF REFADJ RD HBEN INT CH7 D7 CH6 D6 CH5 D5 CH4 D4 CH3 D3/D CH2 D2/D CH D/D9 CH D/D8 GND.µF +.8V TO +3.6V +3V +2.5V 4.7µF OUTPUT STATUS ANALOG INPUTS µp CONTROL INPUTS Typical Operating Circuits CLK CS RD HBEN D7 D6 D5 D4 D3/D D2/D D/D9 D/D8 MAX263 V LOGIC V DD REF REFADJ INT CH3 CH2 CH CH GND.µF +.8V TO +3.6V +3V +2.5V 4.7µF OUTPUT STATUS ANALOG INPUTS µp DATA BUS µp DATA BUS Pin Configurations (continued) Ordering Information (continued) TOP VIEW PART TEMP RANGE PIN-PACKAGE INL (LSB) HBEN 24 V LOGIC MAX263ACEG* C to +7 C 24 QSOP ±.5 D V DD MAX263BCEG* C to +7 C 24 QSOP ± D6 D REF REFADJ MAX263AEEG* -4 C to +85 C 24 QSOP ±.5 MAX263BEEG* -4 C to +85 C 24 QSOP ± * Future product contact factory for availability. D4 5 2 GND D3/D 6 MAX263 9 D2/D 7 8 CH D/D9 8 7 CH D/D8 9 6 CH2 INT 5 CH3 RD 4 CS 2 3 CLK QSOP 9

20 25ksps, +3V, 8-/4-Channel, 2-Bit ADCs Package Information (The package drawing(s) in this data sheet may not reflect the most current specifications. For the latest package outline information, go to QSOP.EPS Maxim cannot assume responsibility for use of any circuitry other than circuitry entirely embodied in a Maxim product. No circuit patent licenses are implied. Maxim reserves the right to change the circuitry and specifications without notice at any time. 2 Maxim Integrated Products, 2 San Gabriel Drive, Sunnyvale, CA Maxim Integrated Products Printed USA is a registered trademark of Maxim Integrated Products.