Linear electronic. Lecture No. 1

Size: px

Start display at page:

Download "Linear electronic. Lecture No. 1"

Helena Brown
6 years ago
Views:

1 1 Lecture No. 1

2 2

3 3

4 4

5 5 Lecture No. 2

6 6

7 7

8 8

9 9

10 10

11 11 Lecture No. 3

12 12

13 13

14 14 Lecture No. 4 Example: find Frequency response analysis for the circuit shown in figure below. Where R S =4kR B1 =8kR B2 =4k R E =3.3kR C =6k R L =4k V CC = 12V, I E 1 ma, o = 100, C= 13.9 pf, Cμ = 2 pf, ro =100 kr π = 2.56kC in = C out = 1F, CE=100F. C in C out 1. Mid-Band Gain Calculation R ' L k But R EF = 0

15 15 Linear electronic k 2.4k 100 A v k 4k 1.31k A Vs 2. Low-Frequency Response 15.9Hz 10 4k 6k 2 1 f 6 out 30Hz k 4k 2 1 f 6 in

16 16 2. High-Frequency Response From here up in frequency, we will start to worry about the details of what s inside the BJT. Now those junction capacitances matter, so one needs to use the full Hybrid- model. C total k 208.5pF R ' s Rin Rs 1.31k 4k 987 R R 1.31k 4k in s f h MHz Also, we will discuss other examples and questions

17 17 Lecture No. 5 Multi-stage "Cascaded" Amplifiers Most practical amplifiers required more gain than can be obtain from a single stage. Consequently, it is common practice to feed the output of one amplifier stage into the input of the next stage. Gain and bandwidth considerations in cascaded amplifiers Most of a cascaded amplifier stages are used to obtain either voltage gain or a current gain. However, in most cascaded amplifiers, ultimately the power gain is important. If a voltage gain is required, we can calculate the total gain by using the equation for voltage gain of one stage. Thus, the voltage gain for stage1 is: Vo1 Av1 Vin1 In addition, the voltage gain for stage 2 is: A v2 V V o2 in2 The gain for additional stages can be written in a similar manner. Then, the total amplifier voltage gain A total for n-cascaded stages is: Vo1 Vo 2 V V o3 o(n1) Vo(n 1)... V V V V V in1 o1 o2 on in1 A total A 1 A 2 A 3... A n In same manner, we can derive the current gain or power gain for the cascaded amplifier. Let f 1 and f 2 is the lower and upper cutoff frequencies, respectively. The voltage or current gain of one stage has been reducing to of its reference value at these frequencies. Now, if we have an amplifier with two identical stages of amplification, the voltage gain at f 1 will be reduced by factor of in each stage. Thus, the amplifier gain at f 1 (and also f 2 ) will be: A v A v2 = 0.5 A total

18 18 Linear electronic For n-identical cascaded stages of amplification, the gain at f 1 and f 2 will be (0.707) n A v. The voltage gain per stage is given for the low frequency by: 1 A o j j A 1 o j 1 1 A A The magnitude of above equation is: 2 1 o ) ( 1 1 A A If there are n-cascaded stages, the magnitude of the total gain amplifier is: n 2 1 n o total ) ( 1 1 A A Now, if ω is to be equal to ω L, the term multiplying A o must be equal to.0707 or 1/(2) 1/2. Then n/ 2 2 L 1 1/ L 1 1/n 1 2 Then, 1 2 n / 1 1 L The voltage gain per stage is given for the low frequency by:

19 19 As similar A A H 2 o 2 j 2 2 1/ n 1 From above equations, ω L will be greater than ω 1 if n is greater than one and ω H will be less than ω 2 if n is greater than one. Thus, the bandwidth of the amplifier decreases as the number of cascaded stages increases. On the other hand, if the amplifier bandwidth is to remain constant, the stage bandwidth must increase as the number of cascaded stages increases. Example: If the f 2 =32MHz, A total =1000, and f H = 12MHz, Calculate mid-band gain "A o n " for n=3 & 7 cascaded stages. Determine the gain per stage for each amplifier. ω 2 = 2π ω H = 2π rad/sec rad/sec A total A n o 1 1 ( H 2 ) 2 n 1. For n= A 3 o A o 3 = A o = For n = 7

20 20 A o 7 = A o =2.865

21 21 Lecture No. 6 PRACTICAL CASCADE AMPLIFIER CIRCUIT In the above figure, let us work out the gain assuming nothing about the R in and R out of each stage, looking at them as voltage dividers between each stage and between the last stage and the load. The equation reduces to the ideal case of A V = A 2 for two identical stages if we let the R o 's go to 0 and the R i 's go to infinity. For example: let R o = 100and R in = 1M, what is the gain with two stages of gain A in series? (Assume RL = 1Mtoo).

22 22 By the time you reached that point, other effects would have caused much more trouble (for example, the fact that noise from each successive stage is add to the noise coming into that stage and amplified... on down the line!). Cascode Amplifier Design Example Specifications: DC power dissipation: PD < 25 mw Power Supply: 12 VDC Voltage Gain: -50X Load: Resistive, 50 K Assume R S = 0 Must use 2N2222A Transistors (NPN, ß = 150 measured) DESIGN PROCESS: 1) Pick V cc unless specified.

23 23 2) Calculate I Max. Vcc= 12 VDC 3) Select an I C < I MAX and solve for g m2. Let I C = 1.8 ma 4) Let R S = 0 and solve for R C : R C = 730 5) Use a 1/4, 1/4, 1/4, 1/4 biasing rule to set up bias resistors. Let V CE of the transistors = V cc /4 = 3V and solve the following for R E. 6) The required base current is: 7) Solve for the biasing resistors.

24 24

25 25 Lecture No. 7 FEEDBACK There are two types of feedback: regenerative (positive feedback) and degenerative (negative feedback). Unless you want your circuit to oscillate, we usually use NEGATIVE FEEDBACK... This idea came about in the late 1920 s when they were able to build amplifiers with reasonable gains, but with gains that were difficult to control from amplifier to amplifier... PROPERTIES OF NEGATIVE FEEDBACK Nonlinear distortion can be reduced. The effects of noise can be reduced (but not the noise itself). The input and output impedances of the amplifier can be modified. The bandwidth of an amplifier can be extended. Of course, if you use negative feedback, overall gain of the amplifier is always less than the maximum achievable by the amplifier without feedback. THE BASIC FEEDBACK CIRCUIT With an input signal x s, an output signal x o, a feedback signal x f, and an amplifier input signal x i, let us look at the basic feedback circuit illustrated above.

26 26 The amplifier has a gain of A and the feedback network has a gain of... The input to the amplifier is, x i = x s - x f The output of the amplifier is, x o = A x i We can obtain an expression for the output signal in terms of the input signal and the feedback gain... x o = A x s - x f = A x s - x o Re-arranging, x o = A x s - Ax o x o (1 + A= A x s From which we obtain the negative feedback equation by solving for the overall gain For positive feedback, you only need to change the + sign in the denominator to a - sign. It is easy to obtain the equation for the feedback signal, x f, If the amplifier gain and the loop gain are large (i.e. A>> 1), then the feedback signal x f becomes nearly an identical copy of the input signal x s. Here we have assumed that there was an input comparator or mixer and an output sampler that provided us with a copy of the output signal for use as a feedback signal. The form these devices take depends upon whether the amplifier s input and output are current or voltage based... We refer to a given feedback amplifier in terms of the MIXING - SAMPLING feedback, where MIXING and SAMPLING are either SHUNT or SERIES... There are four possible types... (For sampling think of how you would measure V or I in the lab... series for current and shunt for voltage).

27 27 TYPES OF MIXER TYPES OF SAMPLER

28 28 Lecture No. 8 INPUT-OUTPUT (MIXING - SAMPLING) SERIES-SHUNT series (voltage) mixing, voltage-sampling V-V SHUNT-SERIES shunt (current) mixing, current-sampling, I-I SERIES-SERIES series (voltage) mixing, current-sampling V-I SHUNT-SHUNT shunt (current) mixing, voltage-sampling I-V Let's consider a familiar example... the common-emitter amplifier. Since we sample the output current and generate a voltage feedback signal, this is a series-series feedback topology. Considering the output current to be the output signal (e.g. i o = i c ) and the input to be v s (for simplicity, assume that R B1 and R B2 are very large), the units of the basic amplifier are, We know that the feedback voltage is given by Ohm's Law as, V f =i o R E so the feedback network gain, = R E (NOTE: don't get confused! This is NOT the transistor's!) Transistor's current gain = i o/ v i g m in -1 The output current is given by:

29 29 i o = g m (v s - v f) = g m (v s - i o R E ) Combining these equations to find the overall gain for the amplifier, G m, we end up with an equation we have seen before! Now that: SERIES-SHUNT FEEDBACK (SERIES [VOLTAGE] MIXING, VOLTAGE-SAMPLING) Two examples are shown below. On the left, the common emitter amplifier connect to feedback circuit consist of (R 1 and R 2 ).

30 30 On the right, the non-inverting operation amplifier configuration using an ideal op-amp (infinite input impedance, zero output impedance)... Vcc RL Vo Vin Q1 NPN R1 R2 RE C1 R2 R1 Notice how you can re-draw the two feedback resistors as a feedback network of the form we are discussing. The feedback network gain can be obtained directly by voltage division,

31 31 Lecture No. 9 This can be plugged into the feedback gain equation to find the overall gain, Continuing with the series-shunt case, but including the input and output resistance terms (R i and R o ). We can obtain an expression for the equivalent input and output resistance...

32 32 The output resistance can also be obtained by the same method we used previously: Reduce the input signal (V s ) to zero and apply a test voltage V t at the output. Starting with the definition, Therefore,

33 33 Lecture No. 10 Power Transistor Amplifier Amplifiers are used to increase the level of a signal and, depending on the increase required; stages are often cascaded to increase the gain. The last stage of the cascade may be required to drive same form of load, for example a loudspeaker, a servomechanism or a coaxial cable for RF applications. Power amplifiers are classified by the nature of the collector current waveform into class A, class B and class C. This classification is explained in the following figure, where a typical transfer characteristic of a transistor amplifier is used. CLASS-A AMPLIFIER The simplest possible circuit of a class-a amplifier is shown in Figure below where R L is the load resistance and R B is the biasing resistance.

34 34 We already know that for the maximum undistorted peak-to-peak output voltage swing the Q-point should be selected on the basis of the following equation: In this equation, R DC is the dc resistance and R AC is the ac resistance in the collector-emitter circuit. Thus, R DC = R AC = R L (In circuit above, there is only one resistance) The collector-to-emitter voltage at the operating point is: When the input signal goes negative, it causes a decrease in the collector current and a corresponding increase in the collectorto-emitter voltage. The ac component of the output voltage is now positive. This situation continues until the collector current reaches zero and the collector-to-emitter voltage becomes equal to V CC.

35 35 This is the maximum value of the collector-to-emitter voltage ignoring the nonlinear operation in the cut-off region. From the above discussion, it should become clear that the output voltage is zero when the input signal is zero and the collector voltage is ½ V CC. At that time, the collector current is I CQ. As the collector current becomes 2I CQ, its ac component has a maximum value of I CQ, and the collector-to-emitter voltage is zero. Thus, the ac component of the output voltage has a minimum value of -½V CC. When the collector current becomes zero, the ac component of the collector current has a minimum value of I CQ, and the ac component of the output voltage attains a maximum value of ½ V CC. With this understanding, we can write the timedomain expressions for the total collector current and total collector-to-emitter voltage as: The instantaneous power dissipated by the transistor is: - Where the first term, ½ I CQ V CC, is the power dissipation at the Q- point when there is no input signal. - The second term, ½ I V CC sin 2 (ωt), is due to the input signal. - Figure below shows a plot of the instantaneous power dissipation by the transistor.

36 36 Since the average value of a sin2 (wt) function is ½, the average power dissipated by the transistor, is: The instantaneous power delivered to the load is: Thus, the average power delivered to the load is: We can substitute for I CQ R L = ½ V CC, and obtain an expression for the maximum value of the average power delivered to the load as: The power supplied by the source is: We can determine the efficiency of the class-a amplifier as: Did you notice that the average power dissipated by the transistor at its Q-point is twice as much as the average power output? For this reason, class-a configuration should be used only when the power output is less than or equal to 1 W.

37 37 Lecture No. 11 Example: Design a common-emitter amplifier that delivers 0.5W power to a 100 resistor. Use a transistor that has a maximum current rating of 500mA, collector-to-emitter saturation voltage of 0.5V, breakdown voltage of 40V, and the common-emitter current gain of 100. Solution: Let us first design the common-emitter amplifier. We have selected a four-resistor bias circuit as shown in Figure below because of its stable operation. The average power supplied to the 100-W load resistor is 0.5 W. then; The maximum current through the transistor is expected to be twice as much, i.e. 200mA during the positive excursion of the collector current. Since the transistor can supply a maximum current of 500mA, it is safe to use this transistor. The undistorted maximum output voltage swing is 10 V (100mA100 ). Let us add a 10% safety factor to the current in order to keep the swing from entering the saturation region on one hand and the

38 38 cut-off region on the other. This will help keep the distortion to its minimum. Therefore, let us select, I CQ = 110mA. - We can now determine the supply voltage as: - At the Q-point, the base current is: ICQ 110mA IBQ 1. 1mA Let us select a current in R 2 that is nearly equal to 10 times the base current R Thus, the current through R1: I I IBQ mA 1 2. We can now compute R1: R V cc Vbe k I The power supplied by the dc source, is: Ps ( ICQ I1 ) Vcc ( ) ma W But: P L =0.5W P 0. 5 Then, L % PS PT ( MAX ) VCC ICQ 11110mA 1. 21W 2 In order to determine the voltage gain, current gain, power gain and input resistance, we can represent the circuit in the midfrequency range by its model as shown in Figure below.

39 39 Since the base current is 1.1mA, the equivalent resistance in the base circuit is: V 25 r T IBQ 1. 1 The base current can now be computed as: Where; circuit. is the equivalent resistance in the emitter The collector current is: The output current is: A v V V o in ( 22. 7/ 101)

40 40 R 16.6 in Thus, the current gain: A I = Finally, the power gain is: A P = A V A I A P =(-73.2) (-440) = 32208

41 41 Lecture No. 12 CLASS B AMPLIFIER One of the major disadvantages of a class-a amplifier is that it dissipates maximum power at its Q-point. The amplifier is consuming power even when there is no signal. In fact, the power consumption goes down only when the input signal is present. We can reduce the power consumption just by biasing the transistor at the cutoff point. At the cutoff point, the voltage drop across the transistor is at its maximum value while the current though it is zero. When an amplifier is biased at its cutoff point, it is called the class-b amplifier. Let us consider the situation when the input voltage begins its positive cycle. For the circuit shown, the transistor will not begin to conduct until the input signal is equal to its base-to-emitter voltage drop V BE. As soon as the input voltage goes above V BE, the transistor turns on and the conduction process begins. The output voltage will simply be V IN V BE. As the input voltage increases, the output voltage increases also and so does the current in the collector.

42 42 The average value of the half-wave collector (load) current is: Thus, the power supplied by the dc voltage source is: The effective (rms) value of the load current is: The power supplied to the load is: It is clear that the efficiency is proportional to the amplitude of

43 43 the collector current. Thus, efficiency would be maximum when I O(Peak) = I ACM. V Then; I CC ACM RL Thus, the maximum power supplied by the dc voltage source is: The maximum power delivered to the load is: We can now compute the maximum efficiency of the class-b amplifier as: The power dissipated by the transistor can be obtained by: Differentiating this equation with respect to I O(Peak) and setting it equal to zero, we obtain the peak value of the collector current that results in maximum power dissipation in the transistor. Example A class-b amplifier of the type shown in Figure below drives a load of 100. It operates from a 15-V dc supply. Assume that the base-to-emitter turn on voltage is essentially zero, is very large, and the output voltage is basically sinusoidal. 1- What is the maximum power it can deliver to the load when its collector-to-emitter saturation voltage is 0.5 V? 2- Efficiency. 3- The average and maximum power dissipated by the transistor.

44 44 Solution: When the base-to-emitter turn on voltage (V BE ) is neglected, the transistor turns on as soon as the input voltage becomes positive. Taking into account the collector-to-emitter saturation [V CE(SAT) ] voltage of 0.5 V into account, the maximum possible output voltage is: The maximum value of the load (collector) current is: The average and rms values of the load current are: The power supplied by the 15-V dc source is: The maximum power delivered to the load is: The efficiency of the class-b amplifier is: The average power dissipated by the transistor is: The maximum power dissipation by the transistor is:

45 45 Lecture No. 13 CLASS-B PUSH-PULL AMPLIFIER As explained in the previous section, the class-b amplifier is better than the class-a amplifier because it has high efficiency. However, the class-b amplifier can only amplify the positive-half of the input signal. In order to be able to amplify the entire signal, we can use two complementary transistors as shown in Figure below. When the input signal is positive, the NPN transistor Q1 turns ON, the PNP transistor Q2 is OFF, and the output voltage is positive. The NPN transistor is pushing the current into the load resistor during the positive cycle of the input voltage. The output voltage can be expressed as: The maximum value of the output voltage is obtained during the positive cycle when the NPN transistor just begins to saturate. That is,

46 46 And As the input voltage falls below V BE, the PNP transistor Q 2 begins to conduct and it pulls the current from the load. The NPN transistor Q 1 pushes the current into the load and the PNP transistor Q 2 pulls the current through it. This is why this circuit configuration is referred to as the Push-Pull amplifier. As the PNP transistor, Q 2 turns ON, the NPN transistor Q 1 cuts off and the output voltage is negative. The saturation voltage of the PNP transistor limits the minimum value of the output voltage. Since we are using the two complementary transistors, we expect the magnitude of the saturation voltage for both transistors to be the same. That is V EC(SAT) of the PNP transistor is equal to V CE(SAT) of the NPN transistor. Thus, the minimum value of the output voltage is: And Let us denote the amplitude (the magnitude of the maximum possible swing) of each output waveform as: The maximum current through each transistor is: The average current through each transistor is:

47 47 Example A class-b push-pull amplifier drives a load of 100. It operates from a dual ± 15V dc supply. Assume that the base-to-emitter turn on voltage is zero, is very large, and the output voltage is essentially sinusoidal. 1- What is the maximum power it can deliver to the load when the collector-to-emitter saturation voltage for each transistor is 0.5 V? 2- Efficiency of power transistor amplifier. Solution: The maximum, unclipped peak-to-peak output voltage that we can obtain from the push-pull amplifier is 29 V. The maximum power delivered to the load is: The total power supplied by the 15-V and the 15 V dc sources is: The efficiency of the class-b amplifier is:

48 48 Lecture No. 14 Logic gates A logic gates is an electronic circuit which make decisions. It has one output and one or more inputs. 1. NOT-Gate It is so called because its output is NOT the same as its input. It is also called inverter because it inverts the input. It has one input and one output as shown in figure below. Figure below

49 49 2. OR-gate The output of this circuit is logic "1" when either one input is logic "1" as shown in figure below. Figure Figure

50 50 AND-gate

51 51

52 52

53 53

54 54

55 55

56 56

55:041 Electronic Circuits The University of Iowa Fall Exam 3. Question 1 Unless stated otherwise, each question below is 1 point.

55:041 Electronic Circuits The University of Iowa Fall Exam 3. Question 1 Unless stated otherwise, each question below is 1 point. Exam 3 Name: Score /65 Question 1 Unless stated otherwise, each question below is 1 point. 1. An engineer designs a class-ab amplifier to deliver 2 W (sinusoidal) signal power to an resistive load. Ignoring