3-Stage Transimpedance Amplifier

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1 3-Stage Transimpedance Amplifier ECE Dr. Maysam Ghovanloo Garren Boggs TEAM 11 Vasundhara Rawat December 11, 2015

2 Project Specifications and Design Approach Goal: Design a 3-stage transimpedance amplifier to amplify input current from a piezoelectric transducer with I s = 5 µa amplitude and 1 MΩ output impedance. The TIA will drive a 50 Ω load with a gain of 1 MΩ. The amplifier should also have a low pass filtering capability to only amplify the ultrasound signals lower than 10 MHz. Stage 1: Common Gate (Required to be FET) Must have an input impedance 100 Ω. This is to maximize the source current entering the amplifier. Common-gate was selected for its low small signal impedance This first stage also allowed for a decent gain. 1 g m. Stage 2: Common Emitter This stage was primarily utilized for high gain. BJT s more commonly produce higher signal gain over FET s. Stage 3: Common Drain Utilized as a current-driving follower circuit in order to match the low load impedance of 50 Ω. The FET s infinite input impedance was very useful as well. Approach: Analyze 4 resistor bias networks to set DC operating points for each stage of the amplifier. Select starting point by setting a key parameter to a desired value, and solving for unknowns using that parameter. Maximize gain for each stage while minimizing power dissipation. Simulate each stage and verify that the results match the by-hand calculations (shown on next slide). Decouple and bypass the DC bias from the AC input signal, and unify all 3 stages. Verify the final result to the project specifications.

3 Figure 1. Mathcad calculations for biasing each stage of the overall TIA amplifier.

4 Finalized 3-Stage Amplifier Circuit The completed 3-stage amplifier design is shown on the right: The input current source is located between Stage 1 and Stage 2. The output load is located to the right of Stage 3. Resistor/capacitor values and transistor parameters used in the design are listed next to their respective components. The circuit was constructed and simulated using Multisim. Figure 2. Multisim schematic of the completed 3-stage amplifier design.

5 Amplifier Gain The gains achieved for each stage are as follows: Stage 1: db = Ω Stage 2: db = Ω Stage 3: db = Ω The overall midband gain for the TIA is: Overall: db = kω While the total gain does not meet the specified 1 MΩ, it comes substantially close. These limitations on gain most likely arise from impedance mismatching, clipping, and limitations on power consumption. Some of the above limitations also describe why the second stage of the TIA would have a lower gain than the first. When the bypass capacitors are removed, the overall midband gain for the TIA is: No Bypass Capacitor Gain: db = kω Figure 3. AC analysis showing the gain provided by each stage, as well as the total amplifier gain. Stage 1 gain is shown in blue. Stage 2 gain is shown in purple. Stage 3 gain is shown green. The total transimpedance gain is shown in red.

6 Input and Load Impedance The input impedance for stage 1 of this amplifier is calculated using: R in = R S 1 g m R in = kΩ Ω (values from Fig. 1) R in = Ω The input impedance to the common gate stage is simply the parallel combination of the source biasing resistor with the small signal input impedance of the transistor. By biasing the first stage the way it is, a large (relative) value for g m was achieved, thus allowing it to be the defining factor for the input impedance. The input impedance of the TIA meets the specified criteria for design of 100 Ω. The load impedance for the output of this amplifier is calculated using: R LOAD = R L R S r o R LOAD = 50Ω Ω 3. 78Ω (values from Fig. 1) R LOAD = 3. 32Ω Taking R L = 50 Ω the load impedance seen at the output is the parallel combination of the connected load, the source biasing resistor, and the small signal output impedance of the transistor. By biasing the third stage the way it is, a very large (relative) value for g m was achieved, thus allowing it to be the defining factor for the load impedance. The load impedance of the TIA permits a large current gain in order to drive the specified 50 Ω load.

7 Bandwidth Analysis The specification for this design regarding bandwidth was that the TIA must act as a low-pass filter for frequencies less than 10 MHz. In order to accomplish this, a shunt capacitor, C shunt, was connected in parallel to the input of stage 3, bypassing some of the AC current to ground. An AC voltage divider had essentially been constructed for high frequencies. In order to determine the value of C shunt, the resistance that this capacitor saw from one terminal to its other was calculated. Then, the cutoff frequency was equated using: f c = 1 2π R cs C shunt Taking f c = 10 MHz, C shunt =.691 pf. The design shows a successful cutoff frequency at 10 MHz with a gain of db from the midband gain. Figure 4. AC analysis showing the 10 MHz bandwidth for the amplifier.

8 Input and Output Voltage Range Ideally the TIA would have an input range of ±5 mv pp (Thevanin equivalent induced from the current source) and an output range of ±5 V pp. However, due to clipping from such a large gain, the actual limits are as such: Input Voltage Range: ±0.23 mv pp Output Voltage Range: 1.78 V pp to 1.87 V pp This discrepancy in the output voltage is due to a linear DC offset built up at the output of each stage. Thus, during the design process in order to maximize these ranges, an attempt was made to zero the DC offset voltages at each of the output nodes (this process can be seen in the calculations in Fig. 1) Bias points were also chosen for each stage, such that they would stay within the forward active or saturation regions of operation. Figure 5. Transient analysis showing the output voltage waveform at the maximum input voltage range (0.23 mv pp ), just before clipping occurs. Figure 6. Transient analysis showing the output voltage waveform at the ideal input voltage range (0.5 mv pp ). Due to circuit limitations, clipping occurs.

9 Rise and Fall Time It is desirable to minimize the rise and fall time, as it has a direct dependence on the speed of a device. This design is no different. The rise and fall times were measured through transient analyses using a step current source. The measured rise and fall times corresponded with the time between obtaining 10% and 90% of the maximum or minimum value of the output. In order to decrease the rise/fall time, the decoupling capacitor at the output must be decreased, to decrease the time constant. However, the tradeoff with this lies with the causation of a smaller bandwidth. Measured Rise Time: μs Measured Fall Time: μs Figure 7. Transient analysis showing the output response to a step wave and its rise time. Figure 8. Transient analysis showing the output response to a step wave and its fall time.

10 Distortion One of the specifications for this design is to have as low of total harmonic distortion as possible. In order to determine the THD of the amplifier, a Fourier analysis was run on the output, using an input signal with a fundamental frequency of 1000 Hz. The value for input signal was chosen to be.23 mv pp, to avoid clipping. Any clipping that would occur would dramatically skew the THD reading. The THD of the amplifier was approximately 8.54%. As the gain of the amplifier increases, clipping becomes more prominent and thus the THD increases. Figure 9. Fourier analysis showing THD and contributions from the first nine harmonics.

11 PSRR and Power Consumption In order to measure the PSRR of the TIA, small AC voltage sources were added in series to the power supplies and the input signal was disconnected. A transient analysis was then run to determine the relative value for the output voltage. The PSRR was then calculated: PSRR + : db PSRR - : db The power consumption for the TIA could be calculated by multiplying the two power supply voltages V dd and V ss, the total DC current that is biasing the three stages. Total Power Consumption: 707 mw The power consumption of the TIA meets the specified criteria for design of 1 W. Figure 10. Mathcad calculations for determining total power consumption.

12 Feedback Implementation Adding feedback to the TIA design will give it more stability, however there are some tradeoffs. In exchange for a larger bandwidth, the feedback reduces the overall midband gain of the TIA. Previously, without feedback this amplifier could not achieve the intended ±5 mv pp input swing. However, with feedback in place, the reduced gain allows the full undistorted output waveform to pass. Figure 11. (Above) Multisim schematic of the TIA design implemented with a shunt feedback system (highlighted in blue). A 700k resistor has been chosen for R F as it maximizes the bandwidth enlargement while minimizing reduction in gain. If the 10 MHz bandwidth is still desired in addition to feedback, the capacitor C shunt can be adjusted until the bandwidth again meets specifications. Figure 12. (Above) AC analysis showing a decrease in TIA gain, but an increase in bandwidth. Figure 13. (Right) Transient analysis showing the ideal input voltage range without clipping.

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