DATASHEET ISL Features. Applications. Ordering Information. Pinout. High Supply Voltage 200MHz Unity-Gain Stable Operational Amplifier

Transcription

1 DATASHEET High Supply Voltage MHz UnityGain Stable Operational Amplifier FN69 Rev. The is a high speed, low power, low cost monolithic operational amplifier. The is unitygain stable and features a V/µs slew rate and MHz bandwidth while requiring only 8.5mA of supply current per amplifier. The power supply operating range of the is from ±5V down to ±.5V. For singlesupply operation, the operates from V down to 5V. The also features an extremely wide output voltage swing of.75v/.v with V S = ±5V and R L =k. At a gain of, the has a db bandwidth of MHz with a phase margin of 55. Because of its conventional voltagefeedback topology, the allow the use of reactive or nonlinear elements in its feedback network. This versatility combined with low cost and ma of outputcurrent drive makes the an ideal choice for pricesensitive applications requiring low power and high speed. The is in a Ld SO (.5 ) package and specified for operation over the full C to 85 C temperature range. Ordering Information PART NUMBER PART MARKING TAPE & REEL PACKAGE PKG. DWG. # IB 55IB Ld SO (.5 ) MDP7 IBT7 55IB 7 Ld SO (.5 ) MDP7 IBT 55IB Ld SO (.5 ) MDP7 IBZ (See Note) IBZT7 (See Note) IBZT (See Note) 55IBZ Ld SO (.5 ) (PbFree) 55IBZ 7 Ld SO (.5 ) (PbFree) 55IBZ Ld SO (.5 ) (PbFree) MDP7 MDP7 MDP7 NOTE: Intersil Pbfree plus anneal products employ special Pbfree material sets; molding compounds/die attach materials and % matte tin plate termination finish, which are RoHS compliant and compatible with both SnPb and Pbfree soldering operations. Intersil Pbfree products are MSL classified at Pbfree peak reflow temperatures that meet or exceed the Pbfree requirements of IPC/JEDEC J STD. Features MHz db bandwidth Unitygain stable Low supply current: 8.5mA per amplifier Wide supply range: ±.5V to ±5V dualsupply and 5V to V singlesupply High slew rate: V/µs Fast settling: 75ns to.% for a V step Wide output voltage swing:.75v/.v with V S = ±5V, R L =k Enhanced replacement for EL Pbfree plus anneal available (RoHS compliant) Applications Video amplifiers Singlesupply amplifiers Active filters/integrators High speed sampleandhold High speed signal processing ADC/DAC buffers Pulse/RF amplifiers Pin diode receivers Log amplifiers Photo multiplier amplifiers Difference amplifiers Pinout OUT IN IN VS IN [ LD SO (.5 )] TOP VIEW 5 OUT IN IN VS IN IN 6 9 IN OUT 7 8 OUT FN69 Rev. Page of

2 Absolute Maximum Ratings (T A = 5 C) Supply Voltage (V S ) ±6.5V or V Input Voltage (V IN) ±V S Differential Input Voltage (dv IN ) ±V Continuous Output Current mA Power Dissipation (P D ) See Curves Operating Temperature Range (T A ) C to 85 C Operating Junction Temperature (T J ) C Storage Temperature (T ST ) C to 5 C CAUTION: Stresses above those listed in Absolute Maximum Ratings may cause permanent damage to the device. This is a stress only rating and operation of the device at these or any other conditions above those indicated in the operational sections of this specification is not implied. IMPORTANT NOTE: All parameters having Min/Max specifications are guaranteed. Typical values are for information purposes only. Unless otherwise noted, all tests are at the specified temperature and are pulsed tests, therefore: T J = T C = T A DC Electrical Specifications V S = ±5V, A V =, R L = k, T A = 5 C, unless otherwise specified. PARAMETER DESCRIPTION CONDITION MIN TYP MAX UNIT V OS Input Offset Voltage V S = ±5V. 5 mv TCV OS Average Offset Voltage Drift (Note ) 7 µv/ C I B Input Bias Current V S = ±5V.6.5 µa I OS Input Offset Current V S = ±5V. µa TCI OS Average Offset Current Drift (Note ). na/ C A VOL Openloop Gain V S = ±5V, V OUT = ±V, R L = k V/V PSRR Power Supply Rejection Ratio V S = ±5V to ±5V 75 db CMRR Commonmode Rejection Ratio V CM = ±V, V OUT = V 75 9 db CMIR Commonmode Input Range V S = ±5V V V OUT Output Voltage Swing V O, R L = k.5. V V O, R L = k.6.75 V V O, R L = V V O, R L = V I SC Output Short Circuit Current 8 ma I S Supply Current (per amplifier) V S = ±5V, no load ma R IN Input Resistance.. M C IN Input Capacitance A V = pf R OUT Output Resistance A V = 5 m PSOR Power Supply Operating Range Dual supply ±.5 ±5 V Single supply.5 V NOTE:. Measured from T MIN to T MAX. AC Electrical Specifications V S = ±5V, A V =, R L = k, T A = 5 C, unless otherwise specified. PARAMETER DESCRIPTION CONDITION MIN TYP MAX UNIT BW db Bandwidth (V OUT =.V PP ) V S = ±5V, A V = MHz V S = ±5V, A V = 55 MHz V S = ±5V, A V = 5 MHz V S = ±5V, A V = 5 7 MHz GBWP Gain Bandwidth Product V S = ±5V 7 MHz PM Phase Margin R L = k, 55 SR Slew Rate (Note ) 6 V/µs FN69 Rev. Page of

3 AC Electrical Specifications V S = ±5V, A V =, R L = k, T A = 5 C, unless otherwise specified. (Continued) PARAMETER DESCRIPTION CONDITION MIN TYP MAX UNIT FPBW Fullpower Bandwidth (Note ) V S = ±5V 9.5 MHz t S Settling to.% (A V = ) V S = ±5V, V step 75 ns dg Differential Gain (Note ) NTSC/PAL. % dp Differential Phase NTSC/PAL.5 en Input Noise Voltage khz nv/ Hz in Input Noise Current khz.5 pa/ Hz NOTES:. Slew rate is measured on rising edge.. For V S = ±5V, V OUT = V PP, for V S = ±5V, V OUT = 5V PP. Fullpower bandwidth is based on slew rate measurement using FPBW = SR/( * V PEAK ).. Video performance measured at V S = ±5V, A V = with two times normal video level across R L = 5. This corresponds to standard video levels across a backterminated 75 load. For other values or R L, see curves. Typical Performance Curves FIGURE. OPENLOOP GAIN vs FREQUENCY FIGURE. OPENLOOP PHASE vs FREQUENCY V S = 5V R F = 5 R L = 5 A V = 5 A V = A V = V S = 5V R F = 5 R L = 5 A V = A V = A V = k M M M G FIGURE. GAIN vs FREQUENCY FOR VARIOUS NON INVERTING GAIN SETTINGS k M M M G FIGURE. GAIN vs FREQUENCY FOR VARIOUS INVERTING GAIN SETTINGS FN69 Rev. Page of

4 Typical Performance Curves (Continued) FIGURE 5. PHASE vs FREQUENCY FOR VARIOUS NON INVERTING GAIN SETTINGS FIGURE 6. PHASE vs FREQUENCY FOR VARIOUS INVERTING GAIN SETTINGS GAIN BANDWIDTH PRODUCT (MHz) 8 6 R L =5 SLEW RATE (V/µs) A V = R F =5 R L =5 C L =5pF POSITIVE SLEW RATE NEGATIVE SLEW RATE SUPPLY VOLTAGES (±V) SUPPLY VOLTAGES (±V) FIGURE 7. GAIN BANDWIDTH PRODUCT vs SUPPLY FIGURE 8. SLEW RATE vs SUPPLY V S = 5V R F = A V = R L = 5 R L = 5 R L = k R L = 5 V S = 5V R F = 5 A V = R L = 5 R L = 5 R L = 5 R L = k k M M M G k M M M G FIGURE 9. GAIN vs FREQUENCY FOR VARIOUS R LOAD (A V = ) FIGURE. GAIN vs FREQUENCY FOR VARIOUS R LOAD (A V = ) FN69 Rev. Page of

5 Typical Performance Curves (Continued) V S = 5V R F = R L = 5 A V = C L = 7pF C L = pf C L = 7pF V S = 5V R F = 5 R L = 5 A V = C L = pf C L = pf C L = 68pF C L = 9pF k M M M G FIGURE. GAIN vs FREQUENCY FOR VARIOUS C LOAD (A V = ) k M M M G FIGURE. GAIN vs FREQUENCY FOR VARIOUS C LOAD (A V = ) V S = 5V R L = 5 A V = R F = 5 R F = 5 R F = R F = V S = 5V R L = 5 A V = R F = 5 R F = k R F = 5 R F = k M M M G FIGURE. GAIN vs FREQUENCY FOR VARIOUS R FEEDBACK (A V = ) k M M M G FIGURE. GAIN vs FREQUENCY FOR VARIOUS R FEEDBACK (A V = ) V S = 5V R F = 5 R L = 5 A V = C IN = pf C IN =.pf C IN = pf C IN = 6.8pF C IN =.7pF R F = R L = 5 A V = V S =.5V V S = V V S = 5V V S = 5V k M M M G FIGURE 5. GAIN vs FREQUENCY FOR VARIOUS INVERTING INPUT CAPACITANCE (C IN ) k M M M G FIGURE 6. GAIN vs FREQUENCY FOR VARIOUS SUPPLY SETTINGS FN69 Rev. Page 5 of

6 Typical Performance Curves (Continued) FIGURE 7. COMMONMODE REJECTION RATIO (CMRR) FIGURE 8. POWER SUPPLY REJECTION RATIO (PSRR) HARMONIC DISTORTION (dbc) V S =±5V A V = R F = R L =5 C L =5pF V OUT =V PP RD HD THD ND HD 5K M M M FIGURE 9. HARMONIC DISTORTION vs FREQUENCY (A V = ) FIGURE. HARMONIC DISTORTION vs OUTPUT VOLTAGE (A V = ) OUTPUT VOLTAGE SWING (Vpp) R L =5 C L =5pF A V = A V = R F = SUPPLY VOLTAGES (±V) FIGURE. OUTPUT SWING vs FREQUENCY FOR VARIOUS GAIN SETTINGS FIGURE. OUTPUT SWING vs SUPPLY VOLTAGE FOR VARIOUS GAIN SETTINGS FN69 Rev. Page 6 of

7 Typical Performance Curves (Continued) % to 8% 8% to % % to 8% 8% to % FIGURE. LARGE SIGNAL RISE AND FALL TIMES FIGURE. SMALL SIGNAL RISE AND FALL TIMES 5 JEDEC JESD5 LOW EFFECTIVE THERMAL CONDUCTIVITY TEST BOARD. TOTAL SUPPLY CURRENT [ma] 5 5 A V = R F = R L =5 C L =5pF POWER DISSIPATION (W) W SO JA = C/W SUPPLY VOLTAGES (±V) FIGURE 5. SUPPLY CURRENT vs SUPPLY VOLTAGE AMBIENT TEMPERATURE ( C) FIGURE 6. PACKAGE POWER DISSIPATION vs AMBIENT TEMPERATURE POWER DISSIPATION (W) JEDEC JESD57 HIGH EFFECTIVE THERMAL CONDUCTIVITY TEST BOARD.8.6.W. SO. JA =88 C/W AMBIENT TEMPERATURE ( C) FIGURE 7. PACKAGE POWER DISSIPATION vs AMBIENT TEMPERATURE FN69 Rev. Page 7 of

8 Product Description The is a wide bandwidth, low power, and low offset voltage feedback operational amplifier. This device is internally compensated for closed loop gain of or greater. Connected in voltage follower mode and driving a 5 load, the db bandwidth is around a MHz. Driving a 5 load and a gain of, the bandwidth is about 9MHz while maintaining a V/µs slew rate. The is designed to operate with supply voltage from 5V to V. That means for single supply application, the supply voltage is from V to V. For split supplies application, the supply voltage is from ±5V. The amplifier has an input commonmode voltage range from.5v above the negative supply (V S pin) to.5v below the positive supply (V S pin). If the input signal is outside the above specified range, it will cause the output signal to be distorted. The outputs of the can swing from.75v to.v for V S = ±5V. As the load resistance becomes lower, the output swing is lower. Choice of Feedback Resistor and Gain Bandwidth Product For applications that require a gain of, no feedback resistor is required. Just short the output pin to the inverting input pin. For gains greater than, the feedback resistor forms a pole with the parasitic capacitance at the inverting input. As this pole becomes smaller, the amplifier's phase margin is reduced. This causes ringing in the time domain and peaking in the frequency domain. Therefore, R F can't be very big for optimum performance. If a large value of R F must be used, a small capacitor in the few Pico Farad range in parallel with R F can help to reduce the ringing and peaking at the expense of reducing the bandwidth. For gain of, R F = is optimum. For the gains other than, optimum response is obtained with R F with proper selection of R F and R G (see Figures5 and 6 for selection). Video Performance For good video performance, an amplifier is required to maintain the same output impedance and the same frequency response as DC levels are changed at the output. This is especially difficult when driving a standard video load of 5, because of the change in output current with DC level. The dg and dp of this device is about.% and.5, while driving 5 at a gain of. Driving high impedance loads would give a similar or better dg and dp performance. Driving Capacitive Loads and Cables The can drive 7pF loads in parallel with 5 with less than db of peaking at gain of and as much as pf at a gain of with under db of peaking. If less peaking is desired in applications, a small series resistor (usually between 5 to 5 ) can be placed in series with the output to eliminate most peaking. However, this will reduce the gain slightly. If the gain setting is greater than, the gain resistor R G can then be chosen to make up for any gain loss which may be created by the additional series resistor at the output. When used as a cable driver, double termination is always recommended for reflectionfree performance. For those applications, a backtermination series resistor at the amplifier's output will isolate the amplifier from the cable and allow extensive capacitive drive. However, other applications may have high capacitive loads without a backtermination resistor. Again, a small series resistor at the output can help to reduce peaking. Output Drive Capability The does not have internal short circuit protection circuitry. It has a typical short circuit current of ma. If the output is shorted indefinitely, the power dissipation could easily overheat the die or the current could eventually compromise metal integrity. Maximum reliability is maintained if the output current never exceeds ±6mA. This limit is set by the design of the internal metal interconnect. Note that in transient applications, the part is robust. Short circuit protection can be provided externally with a back match resistor in series with the output placed close as possible to the output pin. In video applications this would be a 75 resistor and will provide adequate short circuit protection to the device. Care should still be taken not to stress the device with a short at the output. Power Dissipation With the high output drive capability of the, it is possible to exceed the 5 C absolute maximum junction temperature under certain load current conditions. Therefore, it is important to calculate the maximum junction temperature for an application to determine if load conditions or package types need to be modified to assure operation of the amplifier in a safe operating area. The maximum power dissipation allowed in a package is determined according to: T JMAX T AMAX PD MAX = Where: JA T JMAX = Maximum junction temperature T AMAX = Maximum ambient temperature JA = Thermal resistance of the package The maximum power dissipation actually produced by an IC is the total quiescent supply current times the total power supply voltage, plus the power in the IC due to the load, or: For sourcing: n V OUTi PD MAX = V S I SMAX V S V OUTi R Li i = FN69 Rev. Page 8 of

9 For sinking: PD MAX = V S I SMAX V OUTi V S I LOADi Where: V S = Supply voltage I SMAX = Maximum quiescent supply current V OUT = Maximum output voltage of the application R LOAD = Load resistance tied to ground I LOAD = Load current N = number of amplifiers (max = ) n i = By setting the two PD MAX equations equal to each other, we can solve the output current and R LOAD to avoid the device overheat. Caution: For supply voltages greater then V, the maximum power dissipation at 85 C ambient temperature could be exceeded. For higher supply voltages the maximum ambient temperature must be derated according to the Package Power Dissipation curve Figure 7. The maximum power dissipation is highly dependent upon the thermal conductivity of the PCB. For lower thermal conductivity boards use Figure 6. Power Supply Bypassing Printed Circuit Board Layout As with any high frequency device, a good printed circuit board layout is necessary for optimum performance. Lead lengths should be as short as possible. The power supply pin must be well bypassed to reduce the risk of oscillation. For normal single supply operation, where the V S pin is connected to the ground plane, a single.7µf tantalum capacitor in parallel with a.µf ceramic capacitor from V S to GND will suffice. This same capacitor combination should be placed at each supply pin to ground if split supplies are to be used. In this case, the V S pin becomes the negative supply rail. Printed Circuit Board Layout For good AC performance, parasitic capacitance should be kept to minimum. Use of wire wound resistors should be avoided because of their additional series inductance. Use of sockets should also be avoided if possible. Sockets add parasitic inductance and capacitance that can result in compromised performance. Minimizing parasitic capacitance at the amplifier's inverting input pin is very important. The feedback resistor should be placed very close to the inverting input pin. Strip line design techniques are recommended for the signal traces. Application Circuits Sallen Key Low Pass Filter A common and easy to implement filter taking advantage of the wide bandwidth, low offset and low power demands of the. A derivation of the transfer function is provided for convenience (See Figure 8). Sallen Key High Pass Filter Again this useful filter benefits from the characteristics of the. The transfer function is very similar to the low pass so only the results are presented (See Figure 9). Copyright Intersil Americas LLC 5. All Rights Reserved. All trademarks and registered trademarks are the property of their respective owners. For additional products, see Intersil products are manufactured, assembled and tested utilizing ISO9 quality systems as noted in the quality certifications found at Intersil products are sold by description only. Intersil may modify the circuit design and/or specifications of products at any time without notice, provided that such modification does not, in Intersil's sole judgment, affect the form, fit or function of the product. Accordingly, the reader is cautioned to verify that datasheets are current before placing orders. Information furnished by Intersil is believed to be accurate and reliable. However, no responsibility is assumed by Intersil or its subsidiaries for its use; nor for any infringements of patents or other rights of third parties which may result from its use. No license is granted by implication or otherwise under any patent or patent rights of Intersil or its subsidiaries. For information regarding Intersil Corporation and its products, see FN69 Rev. Page 9 of

10 V R k R k C nf C nf R A k R B k V 5V V V C 5 nf C 5 nf V 5V V OUT R 7 k RB K RA Vo K V RCs Vo V Vi Vo Vi K V R R Cs K H(s) RC R Cs (( K)RC RC RC )s H(jw) w RC R C jw(( K)RC RC RC) Holp K wo RC R C Q RC RC RC ( K) RC RC RC FIGURE 8. SALLEN KEY LOW PASS FILTER Holp K wo RC Q K Equations simplify if we let all components be equal R=C V R k R k C nf C nf R A k R B k V 5V V V C 5 nf C 5 nf V 5V V OUT R 7 k Holp K wo RC R C Q RC RC ( K) RC RC K Holp K wo RC Q K RC RC Equations simplify if we let all components be equal R=C FIGURE 9. SALLEN KEY HIGH PASS FILTER FN69 Rev. Page of

11 Differential Output Instrumentation Amplifier The addition of a third amplifier to the conventional three amplifier instrumentation amplifier introduces the benefits of differential signal realization, specifically the advantage of using commonmode rejection to remove coupled noise and ground potential errors inherent in remote transmission. This configuration also provides enhanced bandwidth, wider output swing and faster slew rate than conventional three amplifier solutions with only the cost of an additional amplifier and few resistors. e A R R R R A R e o e o = R R G e e e o = R R G e e e o = R R G e e BW f C = A Di = R R G A Di Strain Gauge The strain gauge is an ideal application to take advantage of the moderate bandwidth and high accuracy of the. The operation of the circuit is very straightforward. As the strain variable component resistor in the balanced bridge is subjected to increasing strain, its resistance changes, resulting in an imbalance in the bridge. A voltage variation from the referenced high accuracy source is generated and translated to the difference amplifier through the buffer stage. This voltage difference as a function of the strain is converted into an output voltage. R G R R REF e o R A e o e A R R FIGURE. DIFFERENTIAL OUTPUT AMPLIFIER VARIABLE SUBJECT TO STRAIN V 5V C 6 nf V 5 V k R 5 R 6 k k k R 7 R 8 k k V V R L k V OUT (VVVV) R F k C nf V 5V FIGURE. STRAIN GAUGE FN69 Rev. Page of

12 Small Outline Package Family (SO) A D h X 5 N (N/) A E E PIN # I.D. MARK c SEE DETAIL X (N/) B. M C A B L C e H A SEATING PLANE GAUGE PLANE.. C. M C A B b A DETAIL X L ± MDP7 SMALL OUTLINE PACKAGE FAMILY (SO) SYMBOL SO8 SO SO6 (.5 ) SO6 (. ) (SOL) SO (SOL) SO (SOL) SO8 (SOL8) TOLERANCE NOTES A MAX A A b c D , E E , e Basic L L Basic h Reference N Reference Rev. L / NOTES:. Plastic or metal protrusions of.6 maximum per side are not included.. Plastic interlead protrusions of. maximum per side are not included.. Dimensions D and E are measured at Datum Plane H.. Dimensioning and tolerancing per ASME Y.5M99 FN69 Rev. Page of