6.976 High Speed Communication Circuits and Systems Lecture 8 Noise Figure, Impact of Amplifier Nonlinearities
|
|
- Justin Fletcher
- 5 years ago
- Views:
Transcription
1 6.976 High Speed Communication Circuits and Systems Lecture 8 Noise Figure, Impact of Amplifier Nonlinearities Michael Perrott Massachusetts Institute of Technology Copyright 2003 by Michael H. Perrott
2 Noise Factor and Noise Figure (From Lec 7) R s e nrs Equivalent output referred current noise (assumed to be independent of Z out and Z L ) Definitions v in Linear,Time Invariant Circuit (Noiseless) Z out i nout Z in v x Z L i out Calculation of SNR in and SNR out
3 Alternative Noise Factor Expression R s e nrs Equivalent output referred current noise (assumed to be independent of Z out and Z L ) v in Linear,Time Invariant Circuit (Noiseless) Z out i nout Z in v x Z L i out From previous slide Calculation of Noise Factor
4 Input Referred Noise Model R s e nrs Equivalent output referred current noise (assumed to be independent of Z out and Z L ) v in Linear,Time Invariant v x Circuit i nout Z in (Noiseless) Z out Z L i out e n i in i s Y s i n Z in v x Linear,Time Invariant Circuit (Noiseless) i out e n Can remove the signal source since Noise Factor can be expressed as the ratio of total output noise to input noise i s Y s i n i in,sc = i out β
5 Input-Referred Noise Figure Expression e n i s Y s i n i in,sc = i out β We know that Let s express the above in terms of input short circuit current
6 Calculation of Noise Factor e n i s Y s i n i in,sc = i out β By inspection of above figure In general, e n and i n will be correlated - Y c is called the correlation admittance
7 Noise Factor Expressed in Terms of Admittances e n i s Y s Y c i u i in,sc = i out β We can replace voltage and current noise currents with impedances and admittances
8 Optimal Source Admittance for Minimum Noise Factor Express admittances as the sum of conductance, G, and susceptance, B Take the derivative with respect to source admittance and set to zero (to find minimum F), which yields Plug these values into expression above to obtain
9 Optimal Source Admittance for Minimum Noise Factor After much algebra (see Appendix L of Gonzalez book for derivation), we can derive - Contours of constant noise factor are circles centered about (G opt,b opt ) in the admittance plane - They are also circles on a Smith Chart (see pp of Gonzalez for derivation and examples) How does (G opt,b opt ) compare to admittance achieving maximum power transfer?
10 Optimizing For Noise Figure versus Power Transfer Signal Source conductance Source susceptance e n i in i s G s B s i n Z in v x Linear,Time Invariant Circuit (Noiseless) i out Source noise produced by source conductance B s Example source admittance for maximum power transfer B opt B max Circles of constant Noise Factor (F min at the center) G max G opt G s One cannot generally achieve minimum noise figure if maximum power transfer is desired
11 Optimal Noise Factor for MOS Transistor Amp Consider the common source MOS amp (no degeneration) considered in Lecture 7 - In Tom Lee s book (pp ), the noise impedances are derived as - The optimal source admittance values to minimize noise factor are therefore
12 Optimal Noise Factor for MOS Transistor Amp (Cont.) Optimal admittance consists of a resistor and inductor (wrong frequency behavior broadband match fundamentally difficult) - If there is zero correlation, inductor value should be set to resonate with C gs at frequency of operation Minimum noise figure - Exact if one defines w t = g m /C gs
13 Recall Noise Factor Comparison Plot From Lecture 7 Noise Factor Scaling Coefficient Versus Q for 0.18 µ NMOS Device 8 Noise Factor Scaling Coefficient c = -j0 c = -j0.55 c = -j1 Note: curves meet if we approximate Q 2 +1 Q 2 Achievable values as a function of Q under the constraint that 1 = w o L g C gs Minimum across all values of Q and 1 L g C gs c = -j0 c = -j0.55 c = -j Q
14 Example: Noise Factor Calculation for Resistor Load Source R s Source R s e nrs e nrl v in R L v out v nout R L Total output noise Total output noise due to source Noise Factor
15 Comparison of Noise Figure and Power Match Source R s Source R s e nrs e nrl v in R L v out v nout R L To achieve minimum Noise Factor To achieve maximum power transfer
16 Example: Noise Factor Calculation for Capacitor Load Source R s Source R s e nrs v in C L v out C L v nout Total output noise Total output noise due to source Noise Factor
17 Example: Noise Factor with Zero Source Resistance Source R L R L e nrl v in C L v out C L v nout Total output noise Total output noise due to source Noise Factor
18 Example: Noise Factor Calculation for RC Load Source R s Source R s e nrs e nrl v in C L R L v out C L v nout R L Total output noise Total output noise due to source Noise Factor
19 Example: Resistive Load with Source Transformer R S Source V s V x V out =NV x 1 R in = RL 2 R out =N 2 R s N R L 1:N Source R S e nrs V x 1:N e nrl 1 R in = RL 2 R out =N 2 V nout =NV x R s N For maximum power transfer (as derived in Lecture 3) R L
20 Noise Factor with Transformer Set for Max Power Transfer Source R S e nrs V x e nrl R in =R s R out =R L V nout = V x R L R L R s Total output noise 1:N= R L R s Total output noise due to source Noise Factor
21 Observations Source R S e nrs V x e nrl R in =R s R out =R L V nout = V x R L R L R s 1:N= R L R s If you need to power match to a resistive load, you must pay a 3 db penalty in Noise Figure - A transformer does not alleviate this issue What value does a transformer provide? - Almost-true answer: maximizes voltage gain given the power match constraint, thereby reducing effect of noise of following amplifiers - Accurate answer: we need to wait until we talk about cascaded noise factor calculations
22 Nonlinearities in Amplifiers We can generally break up an amplifier into the cascade of a memoryless nonlinearity and an input and/or output transfer function V dd R L V out Memoryless Nonlinearity Lowpass Filter V in I d -RL V out V in M 1 I d C L 1+sR L C L Impact of nonlinearities with sine wave input - Causes harmonic distortion (i.e., creation of harmonics) Impact of nonlinearities with several sine wave inputs - Causes harmonic distortion for each input AND intermodulation products
23 Analysis of Amplifier Nonlinearities Focus on memoryless nonlinearity block - The impact of filtering can be added later Memoryless Nonlinearity x y Model nonlinearity as a Taylor series expansion up to its third order term (assumes small signal variation) - For harmonic distortion, consider - For intermodulation, consider
24 Harmonic Distortion Substitute x(t) into polynomial expression Fundamental Harmonics Notice that each harmonic term, cos(nwt), has an amplitude that grows in proportion to A n - Very small for small A, very large for large A
25 Frequency Domain View of Harmonic Distortion A Memoryless Nonlinearity A fund = c 1 A + 3c 3 A 3 4 x 0 w 0 w 2w 3w y Harmonics cause noise - Their impact depends highly on application LNA typically not of consequence Power amp can degrade spectral mask Audio amp depends on your listening preference! Gain for fundamental component depends on input amplitude!
26 1 db Compression Point A Memoryless Nonlinearity A fund = c 1 A + 3c 3 A 3 4 x 0 w 0 w 2w 3w y 20log(A fund ) Definition: input signal level 1 db such that the small-signal gain drops by 1 db - Input signal level is high! 20log(A) A 1-dB Typically calculated from simulation or measurement rather than analytically - Analytical model must include many more terms in Taylor series to be accurate in this context
27 Harmonic Products with An Input of Two Sine Waves DC and fundamental components Second and third harmonic terms Similar result as having an input with one sine wave - But, we haven t yet considered cross terms!
28 Intermodulation Products Second-order intermodulation (IM2) products Third-order intermodulation (IM3) products - These are the troublesome ones for narrowband systems
29 Corruption of Narrowband Signals by Interferers Memoryless Nonlinearity X(w) Interferers Desired Narrowband Signal x y W 0 w 1 w 2 Y(w) Corruption of desired signal 0 w 2 -w 1 w 1 w 2 2w 1 2w 2 3w 1 3w 2 2w 1 -w 2 2w 2 -w 1 w 1 +w 2 2w 1 +w 2 2w 2 +w 1 W Wireless receivers must select a desired signal that is accompanied by interferers that are often much larger - LNA nonlinearity causes the creation of harmonic and intermodulation products - Must remove interference and its products to retrieve desired signal
30 Use Filtering to Remove Undesired Interference Memoryless Nonlinearity X(w) Interferers Desired Narrowband Signal W 0 w 1 w 2 x y Bandpass Filter z Y(w) Corruption of desired signal 0 w 2 -w 1 w 1 w 2 2w 1 2w 2 3w 1 3w 2 2w 1 -w 2 2w 2 -w 1 w 1 +w 2 2w 1 +w 2 2w 2 +w 1 W Z(w) Corruption of desired signal 0 w 2 -w 1 w 1 w 2 2w 1 2w 2 3w 1 3w 2 2w 1 -w 2 2w 2 -w 1 w 1 +w 2 2w 1 +w 2 2w 2 +w 1 Ineffective for IM3 term that falls in the desired signal frequency band W
31 Characterization of Intermodulation Magnitude of third order products is set by c 3 and input signal amplitude (for small A) Magnitude of first order term is set by c 1 and A (for small A) Relative impact of intermodulation products can be calculated once we know A and the ratio of c 3 to c 1 - Problem: it s often hard to extract the polynomial coefficients through direct DC measurements Need an indirect way to measure the ratio of c 3 to c 1
32 Two Tone Test Input the sum of two equal amplitude sine waves into the amplifier (assume Z in of amplifier = R s of source) v in (w) Equal Amplitude Sine Waves 2A Note: v x (w) = v in(w) 2 R s V x Amplifier V out w 1 0 w 2 W V out (w) first-order output third-order IM term v in V bias Z in =R s 2 3 V out =c o +c 1 V x +c 2 V x +c 3 V x 0 w 2 -w 1 w 1 w 2 2w 1 2w 2 3w 1 3w 2 2w 1 -w 2 2w 2 -w 1 w 1 +w 2 2w 1 +w 2 2w 2 +w 1 On a spectrum analyzer, measure first order and third order terms as A is varied (A must remain small) - First order term will increase linearly - Third order IM term will increase as the cube of A W
33 Input-Referred Third Order Intercept Point (IIP3) Plot the results of the two-tone test over a range of A (where A remains small) on a log scale (i.e., db) - Extrapolate the results to find the intersection of the first and third order terms 20log(A fund ) First-order 1 db output = c 1 A Third-order 3 c IM term = 3 A log(A) A 1-dB A iip3 - IIP3 defined as the input power at which the extrapolated lines intersect (higher value is better) Note that IIP3 is a small signal parameter based on extrapolation, in contrast to the 1-dB compression point
34 Relationship between IIP3, c 1 and c 3 Intersection point 20log(A fund ) Solve for A (gives A iip3 ) First-order 1 db output = c 1 A Third-order 3 c IM term = 3 A log(A) A 1-dB A iip3 Note that A corresponds to the peak value of the two cosine waves coming into the amplifier input node (V x ) - Would like to instead like to express IIP3 in terms of power
35 IIP3 Expressed in Terms of Power at Source IIP3 referenced to V x (peak voltage) v in (w) Equal Amplitude Sine Waves 2A Note: v x (w) = v in(w) 2 Amplifier W 0 w 1 w 2 R s V x V out IIP3 referenced to V x (rms voltage) v in V bias Z in =R s 2 3 V out =c o +c 1 V x +c 2 V x +c 3 V x Power across Z in = R s Note: Power from v in
36 IIP3 as a Benchmark Specification Since IIP3 is a convenient parameter to describe the level of third order nonlinearity in an amplifier, it is often quoted as a benchmark spec Measurement of IIP3 on a discrete amplifier would be done using the two-tone method described earlier - This is rarely done on integrated amplifiers due to poor access to the key nodes - Instead, for a radio receiver for instance, one would simply put in interferers and see how the receiver does Note: performance in the presence of interferers is not just a function of the amplifier nonlinearity Calculation of IIP3 is most easily done using a simulator such as Hspice or Spectre - Two-tone method is not necessary simply curve fit to a third order polynomial - Note: two-tone can be done in CppSim
37 Impact of Differential Amplifiers on Nonlinearity v id I 1 I 2 2 M 1 M 2 v x -v id 2 Memoryless Nonlinearity v id I diff = I 2 -I 1 2I bias Assume v x is approximately incremental ground Second order term removed and IIP3 increased!
6.976 High Speed Communication Circuits and Systems Lecture 20 Performance Measures of Wireless Communication
6.976 High Speed Communication Circuits and Systems Lecture 20 Performance Measures of Wireless Communication Michael Perrott Massachusetts Institute of Technology Copyright 2003 by Michael H. Perrott
More informationOutline. Noise and Distortion. Noise basics Component and system noise Distortion INF4420. Jørgen Andreas Michaelsen Spring / 45 2 / 45
INF440 Noise and Distortion Jørgen Andreas Michaelsen Spring 013 1 / 45 Outline Noise basics Component and system noise Distortion Spring 013 Noise and distortion / 45 Introduction We have already considered
More informationHigh Speed Communication Circuits and Systems Lecture 10 Mixers
High Speed Communication Circuits and Systems Lecture Mixers Michael H. Perrott March 5, 24 Copyright 24 by Michael H. Perrott All rights reserved. Mixer Design or Wireless Systems From Antenna and Bandpass
More informationMichael F. Toner, et. al.. "Distortion Measurement." Copyright 2000 CRC Press LLC. <
Michael F. Toner, et. al.. "Distortion Measurement." Copyright CRC Press LLC. . Distortion Measurement Michael F. Toner Nortel Networks Gordon W. Roberts McGill University 53.1
More informationNoise and Distortion in Microwave System
Noise and Distortion in Microwave System Prof. Tzong-Lin Wu EMC Laboratory Department of Electrical Engineering National Taiwan University 1 Introduction Noise is a random process from many sources: thermal,
More informationEECS 242: Analysis of Memoryless Weakly Non-Lineary Systems
EECS 242: Analysis of Memoryless Weakly Non-Lineary Systems Review of Linear Systems Linear: Linear Complete description of a general time-varying linear system. Note output cannot have a DC offset! Time-invariant
More information6.776 High Speed Communication Circuits and Systems Lecture 14 Voltage Controlled Oscillators
6.776 High Speed Communication Circuits and Systems Lecture 14 Voltage Controlled Oscillators Massachusetts Institute of Technology March 29, 2005 Copyright 2005 by Michael H. Perrott VCO Design for Narrowband
More information6.976 High Speed Communication Circuits and Systems Lecture 11 Voltage Controlled Oscillators
6.976 High Speed Communication Circuits and Systems Lecture 11 Voltage Controlled Oscillators Michael Perrott Massachusetts Institute of Technology Copyright 2003 by Michael H. Perrott VCO Design for Wireless
More informationRF, Microwave & Wireless. All rights reserved
RF, Microwave & Wireless All rights reserved 1 Non-Linearity Phenomenon All rights reserved 2 Physical causes of nonlinearity Operation under finite power-supply voltages Essential non-linear characteristics
More informationLow noise amplifier, principles
1 Low noise amplifier, principles l l Low noise amplifier (LNA) design Introduction -port noise theory, review LNA gain/noise desense Bias network and its effect on LNA IP3 LNA stability References Why
More informationIntroduction to Surface Acoustic Wave (SAW) Devices
May 31, 2018 Introduction to Surface Acoustic Wave (SAW) Devices Part 7: Basics of RF Circuits Ken-ya Hashimoto Chiba University k.hashimoto@ieee.org http://www.te.chiba-u.jp/~ken Contents Noise Figure
More informationElectric Circuit Theory
Electric Circuit Theory Nam Ki Min nkmin@korea.ac.kr 010-9419-2320 Chapter 15 Active Filter Circuits Nam Ki Min nkmin@korea.ac.kr 010-9419-2320 Contents and Objectives 3 Chapter Contents 15.1 First-Order
More informationDesigning a 960 MHz CMOS LNA and Mixer using ADS. EE 5390 RFIC Design Michelle Montoya Alfredo Perez. April 15, 2004
Designing a 960 MHz CMOS LNA and Mixer using ADS EE 5390 RFIC Design Michelle Montoya Alfredo Perez April 15, 2004 The University of Texas at El Paso Dr Tim S. Yao ABSTRACT Two circuits satisfying the
More information6.976 High Speed Communication Circuits and Systems Lecture 5 High Speed, Broadband Amplifiers
6.976 High Speed Communication Circuits and Systems Lecture 5 High Speed, Broadband Amplifiers Michael Perrott Massachusetts Institute of Technology Copyright 2003 by Michael H. Perrott Broadband Communication
More informationA 3 5 GHz CMOS High Linearity Ultra Wideband Low Noise Amplifier in 0.18µ CMOS
Proceedings of the 5th WSEAS Int. Conf. on CIRCUITS, SYSTEMS, ELECTRONICS, CONTROL & SIGNAL PROCESSING, Dallas, USA, November -, 6 5 A 5 GHz CMOS High Linearity Ultra Wideband Low Noise Amplifier in.8µ
More informationCHAPTER 3 CMOS LOW NOISE AMPLIFIERS
46 CHAPTER 3 CMOS LOW NOISE AMPLIFIERS 3.1 INTRODUCTION The Low Noise Amplifier (LNA) plays an important role in the receiver design. LNA serves as the first block in the RF receiver. It is a critical
More informationMassachusetts Institute of Technology Department of Electrical Engineering and Computer Science
Massachusetts Institute of Technology Department of Electrical Engineering and Computer Science 6.976 High Speed Communication Circuits and Systems Spring 2003 Homework #4: Narrowband LNA s and Mixers
More informationRF Fundamental Concepts and Performance Parameters
RF Fundamental Concepts and erformance arameters CCE 50 RF and Microwave System Design Dr. Owen Casha B. Eng. (Hons.) h.d. 09/0/0 Overview Introduction Nonlinearity and Time Variance System Noise Thermal
More informationSignals and Systems Lecture 9 Communication Systems Frequency-Division Multiplexing and Frequency Modulation (FM)
Signals and Systems Lecture 9 Communication Systems Frequency-Division Multiplexing and Frequency Modulation (FM) April 11, 2008 Today s Topics 1. Frequency-division multiplexing 2. Frequency modulation
More informationReceiver Architecture
Receiver Architecture Receiver basics Channel selection why not at RF? BPF first or LNA first? Direct digitization of RF signal Receiver architectures Sub-sampling receiver noise problem Heterodyne receiver
More information+ 2. Basic concepts of RFIC design
+ 2. Basic concepts of RFIC design 1 A. Thanachayanont RF Microelectronics + General considerations: 2 Units in RF design n Voltage gain and power gain n Ap and Av are equal if vin and vout appear across
More informationTSEK02: Radio Electronics Lecture 8: RX Nonlinearity Issues, Demodulation. Ted Johansson, EKS, ISY
TSEK02: Radio Electronics Lecture 8: RX Nonlinearity Issues, Demodulation Ted Johansson, EKS, ISY RX Nonlinearity Issues: 2.2, 2.4 Demodulation: not in the book 2 RX nonlinearities System Nonlinearity
More informationTLCE - A3 08/09/ /09/ TLCE - A DDC. IF channel Zc. - Low noise, wide dynamic Ie Vo 08/09/ TLCE - A DDC
Politecnico di Torino ICT School Telecommunication Electronics A3 Amplifiers nonlinearity» Reference circuit» Nonlinear models» Effects of nonlinearity» Applications of nonlinearity Large signal amplifiers
More informationUnderstanding Mixers Terms Defined, and Measuring Performance
Understanding Mixers Terms Defined, and Measuring Performance Mixer Terms Defined Statistical Processing Applied to Mixers Today's stringent demands for precise electronic systems place a heavy burden
More information1. Distortion in Nonlinear Systems
ECE145A/ECE18A Performance Limitations of Amplifiers 1. Distortion in Nonlinear Systems The upper limit of useful operation is limited by distortion. All analog systems and components of systems (amplifiers
More informationIntroduction to CMOS RF Integrated Circuits Design
II. RFIC System Overview Fall 0, Prof. JianJun Zhou II- Outline Introduction RF Transceiver rchitectures RF System Considerations Sensitivity and Selectivity Noise Figure Dynamic Range -db CP and IP Fall
More informationRF/IF Terminology and Specs
RF/IF Terminology and Specs Contributors: Brad Brannon John Greichen Leo McHugh Eamon Nash Eberhard Brunner 1 Terminology LNA - Low-Noise Amplifier. A specialized amplifier to boost the very small received
More informationprint close Chris Bean, AWR Group, NI
1 of 12 3/28/2016 2:42 PM print close Microwaves and RF Chris Bean, AWR Group, NI Mon, 2016-03-28 10:44 The latest version of an EDA software tool works directly with device load-pull data to develop the
More informationTuesday, March 22nd, 9:15 11:00
Nonlinearity it and mismatch Tuesday, March 22nd, 9:15 11:00 Snorre Aunet (sa@ifi.uio.no) Nanoelectronics group Department of Informatics University of Oslo Last time and today, Tuesday 22nd of March:
More informationT he noise figure of a
LNA esign Uses Series Feedback to Achieve Simultaneous Low Input VSWR and Low Noise By ale. Henkes Sony PMCA T he noise figure of a single stage transistor amplifier is a function of the impedance applied
More informationTSEK02: Radio Electronics Lecture 8: RX Nonlinearity Issues, Demodulation. Ted Johansson, EKS, ISY
TSEK02: Radio Electronics Lecture 8: RX Nonlinearity Issues, Demodulation Ted Johansson, EKS, ISY 2 RX Nonlinearity Issues, Demodulation RX nonlinearities (parts of 2.2) System Nonlinearity Sensitivity
More informationSystem analysis and signal processing
System analysis and signal processing with emphasis on the use of MATLAB PHILIP DENBIGH University of Sussex ADDISON-WESLEY Harlow, England Reading, Massachusetts Menlow Park, California New York Don Mills,
More informationAnalysis and Design of Analog Integrated Circuits Lecture 18. Key Opamp Specifications
Analysis and Design of Analog Integrated Circuits Lecture 8 Key Opamp Specifications Michael H. Perrott April 8, 0 Copyright 0 by Michael H. Perrott All rights reserved. Recall: Key Specifications of Opamps
More informationAnsys Designer RF Training Lecture 3: Nexxim Circuit Analysis for RF
Ansys Designer RF Solutions for RF/Microwave Component and System Design 7. 0 Release Ansys Designer RF Training Lecture 3: Nexxim Circuit Analysis for RF Designer Overview Ansoft Designer Advanced Design
More informationClass E/F Amplifiers
Class E/F Amplifiers Normalized Output Power It s easy to show that for Class A/B/C amplifiers, the efficiency and output power are given by: It s useful to normalize the output power versus the product
More information6.976 High Speed Communication Circuits and Systems Lecture 16 Noise in Integer-N Frequency Synthesizers
6.976 High Speed Communication Circuits and Systems Lecture 16 in Integer-N Frequency Synthesizers Michael Perrott Massachusetts Institute o Technology Copyright 23 by Michael H. Perrott Frequency Synthesizer
More informationA Survey of Load Pull Simulation Capabilities How do they Help You Design Power Amplifiers?
A Survey of Load Pull Simulation Capabilities How do they Help You Design Power Amplifiers? Agilent EEsof EDA IMS 2010 MicroApps Andy Howard Agilent Technologies 1 Outline Power amplifier design questions
More information2005 IEEE. Reprinted with permission.
P. Sivonen, A. Vilander, and A. Pärssinen, Cancellation of second-order intermodulation distortion and enhancement of IIP2 in common-source and commonemitter RF transconductors, IEEE Transactions on Circuits
More informationMore notes on intercept points: 11/06 Read these notes with the other related notes ( intermod_notes)
More notes on intercept points: 11/06 Read these notes with the other related notes ( intermod_notes) 1.0 Gain compression: If a signal: x(t) = ACosωt is input to a nonlinear system, we get a nonlinear
More informationApplication Note 106 IP2 Measurements of Wideband Amplifiers v1.0
Application Note 06 v.0 Description Application Note 06 describes the theory and method used by to characterize the second order intercept point (IP 2 ) of its wideband amplifiers. offers a large selection
More informationCHAPTER 4 LARGE SIGNAL S-PARAMETERS
CHAPTER 4 LARGE SIGNAL S-PARAMETERS 4.0 Introduction Small-signal S-parameter characterization of transistor is well established. As mentioned in chapter 3, the quasi-large-signal approach is the most
More informationHigh Dynamic Range Receiver Parameters
High Dynamic Range Receiver Parameters The concept of a high-dynamic-range receiver implies more than an ability to detect, with low distortion, desired signals differing, in amplitude by as much as 90
More informationCHAPTER 14. Introduction to Frequency Selective Circuits
CHAPTER 14 Introduction to Frequency Selective Circuits Frequency-selective circuits Varying source frequency on circuit voltages and currents. The result of this analysis is the frequency response of
More informationToday s menu. Last lecture. Series mode interference. Noise and interferences R/2 V SM Z L. E Th R/2. Voltage transmission system
Last lecture Introduction to statistics s? Random? Deterministic? Probability density functions and probabilities? Properties of random signals. Today s menu Effects of noise and interferences in measurement
More informationHomework Assignment 07
Homework Assignment 07 Question 1 (Short Takes). 2 points each unless otherwise noted. 1. A single-pole op-amp has an open-loop low-frequency gain of A = 10 5 and an open loop, 3-dB frequency of 4 Hz.
More informationDISCRETE DIFFERENTIAL AMPLIFIER
DISCRETE DIFFERENTIAL AMPLIFIER This differential amplifier was specially designed for use in my VK-1 audio oscillator and VK-2 distortion meter where the requirements of ultra-low distortion and ultra-low
More informationIntroduction to CMOS RF Integrated Circuits Design
VII. ower Amplifiers VII-1 Outline Functionality Figures of Merit A Design Classical Design (Class A, B, C) High-Efficiency Design (Class E, F) Matching Network Linearity T/R Switches VII-2 As and TRs
More information3D Distortion Measurement (DIS)
3D Distortion Measurement (DIS) Module of the R&D SYSTEM S4 FEATURES Voltage and frequency sweep Steady-state measurement Single-tone or two-tone excitation signal DC-component, magnitude and phase of
More informationBerkeley. Mixers: An Overview. Prof. Ali M. Niknejad. U.C. Berkeley Copyright c 2014 by Ali M. Niknejad
Berkeley Mixers: An Overview Prof. Ali M. U.C. Berkeley Copyright c 2014 by Ali M. Mixers Information PSD Mixer f c The Mixer is a critical component in communication circuits. It translates information
More informationA New Topology of Load Network for Class F RF Power Amplifiers
A New Topology of Load Network for Class F RF Firas Mohammed Ali Al-Raie Electrical Engineering Department, University of Technology/Baghdad. Email: 30204@uotechnology.edu.iq Received on:12/1/2016 & Accepted
More informationSAMPLE FINAL EXAMINATION FALL TERM
ENGINEERING SCIENCES 154 ELECTRONIC DEVICES AND CIRCUITS SAMPLE FINAL EXAMINATION FALL TERM 2001-2002 NAME Some Possible Solutions a. Please answer all of the questions in the spaces provided. If you need
More informationTexas A&M University Electrical Engineering Department ECEN 665. Laboratory #3: Analysis and Simulation of a CMOS LNA
Texas A&M University Electrical Engineering Department ECEN 665 Laboratory #3: Analysis and Simulation of a CMOS LNA Objectives: To learn the use of s-parameter and periodic steady state (pss) simulation
More informationElectrochemical Impedance Spectroscopy and Harmonic Distortion Analysis
Electrochemical Impedance Spectroscopy and Harmonic Distortion Analysis Bernd Eichberger, Institute of Electronic Sensor Systems, University of Technology, Graz, Austria bernd.eichberger@tugraz.at 1 Electrochemical
More informationFourier Analysis. Chapter Introduction Distortion Harmonic Distortion
Chapter 5 Fourier Analysis 5.1 Introduction The theory, practice, and application of Fourier analysis are presented in the three major sections of this chapter. The theory includes a discussion of Fourier
More informationLecture 17 - Microwave Mixers
Lecture 17 - Microwave Mixers Microwave Active Circuit Analysis and Design Clive Poole and Izzat Darwazeh Academic Press Inc. Poole-Darwazeh 2015 Lecture 17 - Microwave Mixers Slide1 of 42 Intended Learning
More information6.776 High Speed Communication Circuits Lecture 7 High Freqeuncy, Broadband Amplifiers
6.776 High Speed Communication Circuits Lecture 7 High Freqeuncy, Broadband Amplifiers Massachusetts Institute of Technology February 24, 2005 Copyright 2005 by Hae-Seung Lee and Michael H. Perrott High
More information2005 Modelithics Inc.
Precision Measurements and Models You Trust Modelithics, Inc. Solutions for RF Board and Module Designers Introduction Modelithics delivers products and services to serve one goal accelerating RF/microwave
More informationC. Mixers. frequencies? limit? specifications? Perhaps the most important component of any receiver is the mixer a non-linear microwave device.
9/13/2007 Mixers notes 1/1 C. Mixers Perhaps the most important component of any receiver is the mixer a non-linear microwave device. HO: Mixers Q: How efficient is a typical mixer at creating signals
More informationRadio Receiver Architectures and Analysis
Radio Receiver Architectures and Analysis Robert Wilson December 6, 01 Abstract This article discusses some common receiver architectures and analyzes some of the impairments that apply to each. 1 Contents
More informationEfficiently simulating a direct-conversion I-Q modulator
Efficiently simulating a direct-conversion I-Q modulator Andy Howard Applications Engineer Agilent Eesof EDA Overview An I-Q or vector modulator is a commonly used integrated circuit in communication systems.
More informationLecture 6. Angle Modulation and Demodulation
Lecture 6 and Demodulation Agenda Introduction to and Demodulation Frequency and Phase Modulation Angle Demodulation FM Applications Introduction The other two parameters (frequency and phase) of the carrier
More informationNonlinear Macromodeling of Amplifiers and Applications to Filter Design.
ECEN 622(ESS) Nonlinear Macromodeling of Amplifiers and Applications to Filter Design. By Edgar Sanchez-Sinencio Thanks to Heng Zhang for part of the material OP AMP MACROMODELS Systems containing a significant
More informationEE133 - Prelab 3 The Low-Noise Amplifier
Prelab 3 - EE33 - Prof. Dutton - Winter 2004 EE33 - Prelab 3 The Low-Noise Amplifier Transmitter Receiver Audio Amp XO BNC to ANT BNC to ANT XO CO (LM566) Mixer (SA602) Power Amp LNA Mixer (SA602) IF Amp
More informationHighly linear common-gate mixer employing intrinsic second and third order distortion cancellation
Highly linear common-gate mixer employing intrinsic second and third order distortion cancellation Mahdi Parvizi a), and Abdolreza Nabavi b) Microelectronics Laboratory, Tarbiat Modares University, Tehran
More informationTUNED AMPLIFIERS 5.1 Introduction: Coil Losses:
TUNED AMPLIFIERS 5.1 Introduction: To amplify the selective range of frequencies, the resistive load R C is replaced by a tuned circuit. The tuned circuit is capable of amplifying a signal over a narrow
More informationLINEARITY IMPROVEMENT OF CASCODE CMOS LNA USING A DIODE CONNECTED NMOS TRANSISTOR WITH A PARALLEL RC CIRCUIT
Progress In Electromagnetics Research C, Vol. 17, 29 38, 2010 LINEARITY IMPROVEMENT OF CASCODE CMOS LNA USING A DIODE CONNECTED NMOS TRANSISTOR WITH A PARALLEL RC CIRCUIT C.-P. Chang, W.-C. Chien, C.-C.
More informationA Volterra Series Approach for the Design of Low-Voltage CG-CS Active Baluns
A Volterra Series Approach for the Design of Low-Voltage CG-CS Active Baluns Shan He and Carlos E. Saavedra Gigahertz Integrated Circuits Group Department of Electrical and Computer Engineering Queen s
More informationDesign of a Magnetically Tunable Low Noise Amplifier in 0.13 um CMOS Technology
Graduate Theses and Dissertations Iowa State University Capstones, Theses and Dissertations 2012 Design of a Magnetically Tunable Low Noise Amplifier in 0.13 um CMOS Technology Jeremy Brown Iowa State
More informationHigh Frequency Amplifiers
EECS 142 Laboratory #3 High Frequency Amplifiers A. M. Niknejad Berkeley Wireless Research Center University of California, Berkeley 2108 Allston Way, Suite 200 Berkeley, CA 94704-1302 October 27, 2008
More informationDirect-Conversion I-Q Modulator Simulation by Andy Howard, Applications Engineer Agilent EEsof EDA
Direct-Conversion I-Q Modulator Simulation by Andy Howard, Applications Engineer Agilent EEsof EDA Introduction This article covers an Agilent EEsof ADS example that shows the simulation of a directconversion,
More informationAPPLICATION NOTE 3942 Optimize the Buffer Amplifier/ADC Connection
Maxim > Design Support > Technical Documents > Application Notes > Communications Circuits > APP 3942 Maxim > Design Support > Technical Documents > Application Notes > High-Speed Interconnect > APP 3942
More informationIC design for wireless system
IC design for wireless system Lecture 6 Dr. Ahmed H. Madian Ahmed.madian@guc.edu.eg 1 outlines Introduction to mixers Mixer metrics Mixer topologies Mixer performance analysis Mixer design issues Dr. Ahmed
More informationGechstudentszone.wordpress.com
UNIT 4: Small Signal Analysis of Amplifiers 4.1 Basic FET Amplifiers In the last chapter, we described the operation of the FET, in particular the MOSFET, and analyzed and designed the dc response of circuits
More informationAssist Lecturer: Marwa Maki. Active Filters
Active Filters In past lecture we noticed that the main disadvantage of Passive Filters is that the amplitude of the output signals is less than that of the input signals, i.e., the gain is never greater
More informationAppendix. Harmonic Balance Simulator. Page 1
Appendix Harmonic Balance Simulator Page 1 Harmonic Balance for Large Signal AC and S-parameter Simulation Harmonic Balance is a frequency domain analysis technique for simulating distortion in nonlinear
More information2.1 BASIC CONCEPTS Basic Operations on Signals Time Shifting. Figure 2.2 Time shifting of a signal. Time Reversal.
1 2.1 BASIC CONCEPTS 2.1.1 Basic Operations on Signals Time Shifting. Figure 2.2 Time shifting of a signal. Time Reversal. 2 Time Scaling. Figure 2.4 Time scaling of a signal. 2.1.2 Classification of Signals
More informationNoise Specs Confusing?
Noise Specs Confusing? It s really all very simple once you understand it. Then, here s the inside story on noise for those of us who haven t been designing low noise amplifiers for ten years. You hear
More informationIntroduction to Receivers
Introduction to Receivers Purpose: translate RF signals to baseband Shift frequency Amplify Filter Demodulate Why is this a challenge? Interference Large dynamic range required Many receivers must be capable
More informationLecture 20: Passive Mixers
EECS 142 Lecture 20: Passive Mixers Prof. Ali M. Niknejad University of California, Berkeley Copyright c 2005 by Ali M. Niknejad A. M. Niknejad University of California, Berkeley EECS 142 Lecture 20 p.
More informationHigh Gain Low Noise Amplifier Design Using Active Feedback
Chapter 6 High Gain Low Noise Amplifier Design Using Active Feedback In the previous two chapters, we have used passive feedback such as capacitor and inductor as feedback. This chapter deals with the
More informationAnalysis and Design of Analog Integrated Circuits Lecture 8. Cascode Techniques
Analysis and Design of Analog Integrated Circuits Lecture 8 Cascode Techniques Michael H. Perrott February 15, 2012 Copyright 2012 by Michael H. Perrott All rights reserved. Review of Large Signal Analysis
More informationTransformer Waveforms
OBJECTIVE EXPERIMENT Transformer Waveforms Steady-State Testing and Performance of Single-Phase Transformers Waveforms The voltage regulation and efficiency of a distribution system are affected by the
More informationPARAMETRIC MEASUREMENT OF CLASS-T AMPLIFIERS
PARAMETRIC MEASUREMENT OF CLASS-T AMPLIFIERS Revised: March 000 Copyright 997-000 Tripath Technology, Inc All Rights Reserved Introduction Audio amplifiers are commonly specified by and evaluated against
More informationTSEK03: Radio Frequency Integrated Circuits (RFIC) Lecture 5-6: Mixers
TSEK03: Radio Frequency Integrated Circuits (RFIC) Lecture 5-6: Mixers Ted Johansson, EKS, ISY ted.johansson@liu.se Overview 2 Razavi: Chapter 6.1-6.3, pp. 343-398. Lee: Chapter 13. 6.1 Mixers general
More informationLab Project EE348L. Spring 2005
Lab Project EE348L Spring 2005 B. Madhavan Spring 2005 B. Madhavan Page 1 of 7 EE348L, Spring 2005 1 Lab Project 1.1 Introduction Based on your understanding of band pass filters and single transistor
More informationLeveraging High-Accuracy Models to Achieve First Pass Success in Power Amplifier Design
Application Note Leveraging High-Accuracy Models to Achieve First Pass Success in Power Amplifier Design Overview Nonlinear transistor models enable designers to concurrently optimize gain, power, efficiency,
More informationElectronics basics for MEMS and Microsensors course
Electronics basics for course, a.a. 2017/2018, M.Sc. in Electronics Engineering Transfer function 2 X(s) T(s) Y(s) T S = Y s X(s) The transfer function of a linear time-invariant (LTI) system is the function
More information6.776 High Speed Communication Circuits Lecture 6 MOS Transistors, Passive Components, Gain- Bandwidth Issue for Broadband Amplifiers
6.776 High Speed Communication Circuits Lecture 6 MOS Transistors, Passive Components, Gain- Bandwidth Issue for Broadband Amplifiers Massachusetts Institute of Technology February 17, 2005 Copyright 2005
More informationELEN 701 RF & Microwave Systems Engineering. Lecture 8 November 8, 2006 Dr. Michael Thorburn Santa Clara University
ELEN 701 RF & Microwave Systems Engineering Lecture 8 November 8, 2006 Dr. Michael Thorburn Santa Clara University System Noise Figure Signal S1 Noise N1 GAIN = G Signal G x S1 Noise G x (N1+No) Self Noise
More informationNormally, when linearity behavior of an
ICROWAVE JOURAL REVIEWED EDITORIAL BOARD TECHICAL FEATURE COPACT FORULAS TO RELATE ACPR AD PR TO TWO-TOE IR AD IP A set of compact formulas are presented to estimate modern multitone distortion figures
More informationMini Project 3 Multi-Transistor Amplifiers. ELEC 301 University of British Columbia
Mini Project 3 Multi-Transistor Amplifiers ELEC 30 University of British Columbia 4463854 November 0, 207 Contents 0 Introduction Part : Cascode Amplifier. A - DC Operating Point.......................................
More informationHigh-Linearity CMOS. RF Front-End Circuits
High-Linearity CMOS RF Front-End Circuits Yongwang Ding Ramesh Harjani iigh-linearity CMOS tf Front-End Circuits - Springer Library of Congress Cataloging-in-Publication Data A C.I.P. Catalogue record
More informationOutcomes: Core Competencies for ECE145A/218A
Outcomes: Core Competencies for ECE145A/18A 1. Transmission Lines and Lumped Components 1. Use S parameters and the Smith Chart for design of lumped element and distributed L matching networks. Able to
More informationNoise. Interference Noise
Noise David Johns and Ken Martin University o Toronto (johns@eecg.toronto.edu) (martin@eecg.toronto.edu) University o Toronto 1 o 55 Intererence Noise Unwanted interaction between circuit and outside world
More informationLSJ689. Linear Systems. Application Note. By Bob Cordell. Three Decades of Quality Through Innovation
Three Decades of Quality Through Innovation P-Channel Dual JFETs Make High-Performance Complementary Input Stages Possible Linear Systems Lower Current Noise Lower Bias Current Required LSJ689 Application
More informationLecture 17: BJT/FET Mixers/Mixer Noise
EECS 142 Lecture 17: BJT/FET Mixers/Mixer Noise Prof. Ali M. Niknejad University of California, Berkeley Copyright c 2005 by Ali M. Niknejad A. M. Niknejad University of California, Berkeley EECS 142 Lecture
More informationSP 22.3: A 12mW Wide Dynamic Range CMOS Front-End for a Portable GPS Receiver
SP 22.3: A 12mW Wide Dynamic Range CMOS Front-End for a Portable GPS Receiver Arvin R. Shahani, Derek K. Shaeffer, Thomas H. Lee Stanford University, Stanford, CA At submicron channel lengths, CMOS is
More informationHomework Assignment 03
Homework Assignment 03 Question 1 (Short Takes), 2 points each unless otherwise noted. 1. Two 0.68 μf capacitors are connected in series across a 10 khz sine wave signal source. The total capacitive reactance
More informationMixer. General Considerations V RF VLO. Noise. nonlinear, R ON
007/Nov/7 Mixer General Considerations LO S M F F LO L Noise ( a) nonlinearity (b) Figure 6.5 (a) Simple switch used as mixer (b) implementation of switch with an NMOS device. espect to espect to It is
More informationNarrowband CMOS RF Low-Noise Amplifiers
Narrowband CMOS RF Low-Noise Amplifiers Prof. Thomas H. Lee Stanford University tomlee@ee.stanford.edu http://www-smirc.stanford.edu Outline A brief review of classic two-port noise optimization Conditions
More information