Control of Circulating Current in Two Parallel Three-Phase Boost Rectifiers

Transcription

1 IEEE TRANSACTIONS ON POWER ELECTRONICS, VOL. 17, NO. 5, SEPTEMBER Control of Circulating Current in Two Parallel Three-Phase Boost Rectifiers Zhihong Ye, Member, IEEE, Dushan Boroyevich, Member, IEEE, Jae-Young Choi, Member, IEEE, and Fred C. Lee, Fellow, IEEE Abstract One unique feature in parallel three-phase converters is a potential zero-sequence circulating current. To avoid the circulating current, most present technology uses isolation approach, such as transformers or separate power supplies. This paper proposes a parallel system where individual converters connect both ac and dc sides directly without additional passive components to reduce size and cost of the overall parallel system. In this case, the control of the circulating current becomes an important objective in the converter design. This paper 1) develops an averaged model of the parallel converters based on a phase-leg averaging technique; 2) a zero-sequence model is then developed to predict the dynamics of the zero-sequence current; 3) based on the zero-sequence model, this paper introduces a new control variable, which is associated with space-vector modulation; 4) a strong zero-sequence current control loop is designed to suppress the circulating current; 5) simulation and experimental results validate the developed model and the proposed control scheme. Index Terms Boost rectifier, parallel three-phase converters, phase-leg, space vector modulation (SVM), variable zero-vectors, zero-sequence circulating current. I. INTRODUCTION THE use of parallel power converters, particularly parallel dc/dc converters, has become more common in the past decade. However, the use of parallel three-phase converters has not yet been explored extensively. One unique feature when paralleling three-phase converters is a potential zero-sequence circulating current [1] [12]. To avoid the circulating current, the following three approaches are used commonly with present technology: 1) Isolation. Separate ac or dc power supplies [2], [11], or a transformer isolated ac side [3], [5] is configured for the overall parallel system. In this approach, the overall parallel system is bulky and costly because of additional power supplies or the ac line-frequency transformer. Manuscript received December 1, 2000; revised May 1, Recommended by Associate Editor Y.-F. Liu. Z. Ye is with the General Electric Corporate Research and Development, Niskayuna, NY USA ( ye@crd.ge.com). D. Boroyevich and F. C. Lee are with the Center for Power Electronics Systems (CPES), The Bradley Department of Electrical and Computer Engineering, Virginia Polytechnic Institute and State University, Blacksburg, VA USA. J.-Y. Choi is with the Research and Development Center, Samsung Electronics Company, Ltd., Kyunggi-Do , Korea. Publisher Item Identifier /TPEL Fig. 1. Directly parallel three-phase boost rectifier system. 2) High impedance. Inter-phase reactors are used to provide high zero-sequence impedance [1], [6]. However, the reactors provide high impedance only at medium and high frequencies. They cannot prevent a low-frequency circulating current. 3) Synchronized control. This approach basically treats the parallel converters as one converter [4], [5], [7] [10]. For example, two parallel three-phase three-leg converters are controlled as a three-phase six-leg converter. This approach is not suitable for modular converter design. When more converters are in parallel, the system becomes very complicated to design and control. This paper proposes a parallel system where individual converters connect both ac and dc sides directly without additional passive components. The direct connection would reduce size and cost. Meanwhile, the parallel converters are controlled independently to facilitate modular design. In Section II, an averaged model of the zero-sequence current in two parallel three-phase boost rectifiers, as shown in Fig. 1, is developed. Based on the model, Section III introduces a new control variable, which is associated with space-vector modulation. Then, a zero-sequence current control scheme is proposed. The control scheme is designed within an individual converter in order to have modular design. Section IV shows some simulation and experimental results to validate the developed model and the proposed control scheme. Section V summarizes the major contributions of this work and discusses ideas for future work /02$ IEEE

2 610 IEEE TRANSACTIONS ON POWER ELECTRONICS, VOL. 17, NO. 5, SEPTEMBER 2002 Fig. 3. Averaged phase-leg model of a three-phase boost rectifier. in Fig. 2, where the lower case symbols represent instantaneous variables, and the upper case symbols represent averaged variables. Fig. 2 shows one totem pole phase-leg of the rectifier. It has a current source in one side and a voltage source in the other. Both current and voltage are assumed continuous. Fig. 2 shows the pulse-width modulation (PWM) of the switches, where is defined as the duty cycle of the top switch, while is complementary with. The corresponding voltage and current relationships are also shown in Fig. 2. Based on these relationships, the averaged model of the phaseleg is depicted in Fig. 2(c). Applying phase-leg averaging to all three legs of the rectifier, an averaged model of the rectifier is developed, as shown in Fig. 3. For a carrier-based PWM rectifier, the duty cycles and are sinusoidal in steady state under balanced condition. Therefore, the sum of, and is zero. A space-vector modulated rectifier, however, usually has triple harmonics in order to reduce switching losses, increase maximum modulation index, and improve waveforms total harmonic distortion (THD). Therefore, the sum of the duty cycles is not equal to zero, and it is defined as a zero-sequence duty-cycle (1) From (1), the following equation can be easily derived: (2) That is (c) (3) Fig. 2. Totem pole phase-leg averaging technique. Totem pole phase-leg cell. Switching pulses and the relationships between input and output variables. (c) Averaged phase-leg model. where, and are II. MODELING OF THE ZERO-SEQUENCE CURRENT A traditional modeling approach for a three-phase boost rectifier is to transform stationary variables into rotating coordinates. Zero-sequence components, such as zero-sequence voltage, are not reflected in the model because they do not affect control objectives, such as input line currents and output dc voltage. In order to model the zero-sequence current for the parallel rectifiers, a phase-leg averaging technique is used [12], as illustrated Therefore,, and can be expressed as (4) (5)

3 YE et al.: CONTROL OF CIRCULATING CURRENT 611 Fig. 4. Averaged model of a three-phase PWM boost rectifier with zero-sequence components. Fig. 5. Averaged model of the parallel rectifiers based on phase-leg averaging. As a result, Fig. 4 shows the averaged model of the threephase rectifier with zero-sequence components. For a single rectifier, the sum of and has to be zero because there is no zero-sequence current path. Although a zero-sequence voltage exists in the converter, it does not affect the input currents and output voltage control. With two rectifiers in parallel, a zero-sequence current path is formed and a circulating current may occur. Fig. 5 shows the averaged model of the two parallel three-phase rectifiers. In Fig. 5, the zero-sequence current is defined as and (8) (9) In the ac side, there are three loops forming three equations (6) where and, which are not identified as a separate circuit element in Fig. 5, are equivalent series resistors (ESR s) of the inductors and, respectively. Summing up (7) (9), and using (3) and (6), the following equation can be derived: (7) (10)

4 612 IEEE TRANSACTIONS ON POWER ELECTRONICS, VOL. 17, NO. 5, SEPTEMBER 2002 Fig. 6. Averaged model of the zero-sequence dynamic. Fig. 8. Definition of the new control variable k. Fig. 9. Averaged zero-sequence model with the new control variable k. Fig. 7. Duty cycle relationship between phase-legs and space vectors. Equation (10) describes the dynamic of the zero-sequence components. As a result, the averaged model of the zero-sequence dynamic is developed, and is depicted in Fig. 6. III. CONTROL OF THE ZERO-SEQUENCE CURRENT Different space-vector modulation (SVM) schemes produce different triple harmonics and therefore have different duty cycles, and. For example, Fig. 7 shows one PWM pattern of the SVM scheme with alternative zero vectors. The, and are the duty cycles of and, respectively (11) where and are the duty cycles of the active vectors and, respectively, and is the total duty cycle of the zero vectors and. In this case, is (12) Although different SVM schemes have the same and in the synthesis of a reference vector, can differ. The distribution of the zero vectors can vary without affecting the control objectives, such as the input ac currents and the output dc voltage. This indicates that can be controlled by the distribution of. Based on this idea, a new control variable is introduced as follows: (13) Fig. 10. Implementation of the common-sequence control. where is the time period for applying the zero vector, as illustrated in Fig. 8. Usually, for the scheme with alternative zero vectors,, as shown in Fig. 7. With the definition in (13), (12) can be rewritten as (14)

5 YE et al.: CONTROL OF CIRCULATING CURRENT 613 Fig. 11. Simulated waveforms without zero-sequence current control (f = 32 khz, f = 16 khz). Zero-sequence currents. Input phase currents. Then, the difference of of the two rectifiers is expressed as (15) As a result, the new averaged model of the zero-sequence dynamic with the new control variable is shown in Fig. 9. Since it is a first-order system, the control bandwidth of the zero-sequence current loop can be designed to be very high and a strong current loop suppressing the zero-sequence current can be achieved. One rectifier needs only two current sensors to implement power factor correction because the sum of the three line currents is always zero. With two rectifiers in parallel, three current sensors are needed in order to obtain the zero-sequence current. Fig. 10 shows the implementation of the zero-sequence current control. In a two-parallel converter system, it is sufficient to control one of the two converters since there is only one zero-sequence current. The shaded block is the zero-sequence current controller added onto the other control parts of the rectifier. This control scheme is advantageous over the one that treats the parallel converters as one converter. Since this scheme Fig. 12. Simulated waveforms with zero-sequence current control (f = 32 khz, f =16kHz). The zero-sequence currents. The input phase currents. is implemented within the individual converter and does not need any additional interconnected circuitry, it allows modular design. IV. SIMULATION AND EXPERIMENTAL RESULTS The simulation model was developed using SABER. Without the zero-sequence current control, any discrepancies between two rectifiers (different switching frequencies, different power stage parameters or different switching deadtime, for example, each of which was demonstrated in simulation) may cause a large circulating current. Fig. 11 shows two rectifiers with switching frequencies of 32 khz and 16 khz. Fig. 11 shows that a significant low-frequency circulating current exists in the system. The and are zero-sequence currents for rectifiers 1 and 2, respectively. The circulating current causes distorted input line currents and, as shown in Fig. 11. By applying the zero-sequence current control, the waveforms in Fig. 12 show that the circulating current is almost gone. Only high-frequency current ripples still exist, and they can be easily attenuated.

6 614 IEEE TRANSACTIONS ON POWER ELECTRONICS, VOL. 17, NO. 5, SEPTEMBER 2002 Fig. 13. Experimental waveforms without zero-sequence current control (f =32kHz, f =16kHz, unsynchronized). The zero-sequence currents. The input phase currents. The experimental results are shown in Figs. 13 and 14. A twoparallel, three-phase boost rectifier breadboard system was built and tested. The converters specifications are shown as follows: Input voltage: V. Output voltage: V. Rated power: 15 kw/converter. Switching frequency: 16 khz or 32 khz. Input inductor: 256 H. Output capacitor: 1200 F. IGBT modules: TOSHIBA MG 150J2YS50. DSP: ADSP2101. Fig. 13 shows the zero-sequence currents and the line currents without zero-sequence current control, whereas Fig. 14 shows the waveforms with control. Due to nonuniform practical conditions (such as different delays of clock signals), the experimental waveforms are less uniform than simulation waveforms. Also, three noticeable ripples in Fig. 14 are due to distortion introduced by zero-crossing detection. Fig. 14. Experimental waveforms with zero-sequence current control (f = 32 khz, f = 16 khz, unsynchronized). The zero-sequence currents. The input phase currents. V. CONCLUSION This work has developed an averaged model to predict zerosequence dynamics in two parallel three-phase boost rectifiers. To control the zero-sequence current, a new control variable associated with space-vector modulation was introduced. Since the zero-sequence dynamic is a first-order system, a high bandwidth control loop was designed to effectively suppress the circulating current. Both simulation and experimental results validated the proposed control scheme. The implementation requires only one additional current sensor. The control algorithm can be easily programmed in a digital signal processor (DSP). This modeling approach and control concept can be generalized for paralleling any two multi-phase converters, such as full bridge rectifiers and inverters, three-phase three-leg rectifiers and inverters, and three-phase four-leg rectifiers and inverters. These converters cover most medium and high power applications, such as motor drives, ac power supplies and dc power supplies. The generalization of this concept will be reported in a separate paper. REFERENCES [1] K. Matsui, A pulse width modulated inverter with parallel-connected transistors by using sharing reactors, in Proc. IEEE Ind. Applicat. Soc. Annu. Meeting, Toronto, ON, Canada, 1985, pp

7 YE et al.: CONTROL OF CIRCULATING CURRENT 615 [2] T. Kawabata and S. Higashino, Parallel operation of voltage source inverters, IEEE Trans. Ind. Applicat., vol. 24, pp , Mar./Apr [3] J. W. Dixon and B. T. Ooi, Series and parallel operation of hysteresis current-controlled PWM rectifiers, IEEE Trans. Ind. Applicat., vol. 25, pp , July/Aug [4] S. Ogasawara, J. Takagaki, and H. Akagi, A novel control scheme of a parallel current-controlled PWM inverter, IEEE Trans. Ind. Applicat., vol. 28, pp , Sept./Oct [5] Y. Komatsuzaki, Cross current control for parallel operating three-phase inverter, in Proc. 25th Annu. IEEE Power Electron. Spec. Conf., 1994, pp [6] Y. Sato and T. Kataoka, Simplified control strategy to improve ac-inputcurrent waveform of parallel-connected current-type PWM rectifiers, Proc. Inst. Elect. Eng., vol. 142, pp , July [7] L. Matakas Jr. and E. Masada, Analysis of the parallel connection of 3-phase VSC converters, in Proc. Int. Power Electron. Congr. (IPEC), 1995, pp [8] L. Matakas Jr. and W. Kaiser, Low harmonics, decoupled histeresis type current control of a multi-converter consisting of a parallel transformerless connection of VSC converters, in Proc. IEEE Ind. Applicat. Soc. Annu. Meeting, New Orleans, LA, 1997, pp [9] S. Fukuda and K. Matsushita, A control method for parallel-connected multiple inverter systems, in Proc. Power Electron. Variable Speed Drive Conf., London, U.K., 1998, pp [10] R. Abe, Y. Nagai, and K. Tsuyuki, Development of multiple space vector control for direct connected parallel current source power converters, in Proc. Power Conv. Conf., vol. 1, 1997, pp [11] C. S. Lee et al., Parallel UPS with an instantaneous current sharing control, in Proc. 24th Annu. Conf. IEEE Ind. Electron. Soc., vol. 1, 1998, pp [12] K. Xing, Modeling, Analysis and Design of Distributed Power Electronics System Based on Building Block Concept, Ph.D. dissertation, Virginia Polytech. Inst. and State Univ., Blacksburg, May Zhihong Ye (S 98 M 00) received the B.S. and M.S. degrees in electrical engineering from Tsinghua University, Beijing, China, in 1992 and 1994, respectively, and the Ph.D. degree from the Virginia Polytechnic Institute and State University (Virginia Tech), Blacksburg, in Prior to joining Virginia Tech in 1996, he was a Research Assistant with the Department of Electrical and Applied Electronics Engineering, Tsinghua University. Since September 2000, he has been with General Electric Corporate Research and Development Center, Niskayuna, NY, where he is involved with several alternative energy and distributed generation programs, including power conditioning systems design for fuel cell and microturbine, distributed generation, and grid interconnection studies, etc. His research interests are multiphase power conversion, power conditioning systems for alternative energy, stability, and interaction analysis of distributed power electronics systems. Dr. Ye is a member of Sigma Xi and the IEEE Power Electronics, Industry Applications, Industrial Electronics, and Power Engineering Societies. Dushan Boroyevich (M 82) received the B.S. degree from the University of Belgrade, Yugoslavia, in 1976, the M.S. degree from the University of Novi Sad, Yugoslavia, in 1982, and the Ph.D. degree from the Virginia Polytechnic Institute and State University (Virginia Tech), Blacksburg, in Between 1986 and 1990, he was an Assistant Professor and Director of the Power and Industrial Electronics Research Program, Institute for Power and Electronic Engineering, University of Novi Sad, and later, acting head of the Institute. In 1990, he joined The Bradley Department of Electrical and Computer Engineering, Virginia Tech, as an Associate Professor. From 1996 to 1998, he was Associate Director of Virginia Power Electronics Center, and since 1998 he has been the Deputy Director of the NSF Engineering Research Center for Power Electronics Systems and Professor at the department. His research interests include multiphase power conversion, high-power PWM converters, modeling and control of power converters, applied digital control, and electrical drives. He has published over 100 technical papers, has three patents, and has been involved in numerous government and industry-sponsored projects in the areas of power and industrial electronics. Dr. Boroyevich is a member of Phi Kappa Phi, the IEEE Power Electronics Society AdCom, and the IEEE Industry Applications Society Industrial Power Converter Committee. Jae-Young Choi (M 01) was born in Ulsan-City, Korea, on May 5, He received the B.S. and M.S. degrees from Seoul National University, Korea, in 1988 and 1990, respectively, and the Ph.D. degree from the Virginia Polytechnic Institute and State University (Virginia Tech), Blacksburg, in He worked for LG Electronics, Ltd., Korea as a Research Engineer from 1990 to 1996 and for CPES, Virginia Tech, as a Research Assistant from 1996 to Since 2001, he has been a Principal Engineer at Samsung Electronics, Ltd., Korea. His research interests are soft-switching topologies for multiphase converters, motor control, and power distribution systems. Dr. Choi is a member of both the IEEE Power Electronics Society and the IEEE Industry Applications Society. Fred C. Lee (S 72 M 74 SM 87 F 90) received the the B.S. degree in electrical engineering from the National Cheng Kung University, Taiwan, R.O.C., in 1968 and the M.S. and Ph.D. degrees in electrical engineering from Duke University, Durham, NC, in 1971 and 1974, respectively. He is a University Distinguished Professor with Virginia Polytechnic Institute and State University (Virginia Tech), Blacksburg, and prior to that he was the Lewis A. Hester Chair of Engineering at Virginia Tech. He directs the Center for Power Electronics Systems (CPES), a National Science Foundation engineering research center whose participants include five universities and over 100 corporations. He is also the Founder and Director of the Virginia Power Electronics Center (VPEC), one of the largest university-based power electronics research centers in the country. Total sponsored research funding secured by him over the last 20 years exceeds $35 million. His research interests include high-frequency power conversion, distributed power systems, space power systems, power factor correction techniques, electronics packaging, high-frequency magnetics, device characterization, and modeling and control of converters. He holds 19 U.S. patents, and has published over 120 journal articles in refereed journals and more than 300 technical papers in conference proceedings. Dr. Lee received the Society of Automotive Engineering s Ralph R. Teeter Education Award (1985), Virginia Tech s Alumni Award for Research Excellence (1990), and its College of Engineering Dean s Award for Excellence in Research (1997), in 1989, the William E. Newell Power Electronics Award, the highest award presented by the IEEE Power Electronics Society for outstanding achievement in the power electronics discipline, the Power Conversion and Intelligent Motion Award for Leadership in Power Electronics Education (1990), the Arthur E. Fury Award for Leadership and Innovation in Advancing Power Electronic Systems Technology (1998), the IEEE Millennium Medal, and honorary professorships from Shanghai University of Technology, Shanghai Railroad and Technology Institute, Nanjing Aeronautical Institute, Zhejiang University, and Tsinghua University. He is an active member in the professional community of power electronics engineers. He chaired the 1995 International Conference on Power Electronics and Drives Systems, which took place in Singapore, and co-chaired the 1994 International Power Electronics and Motion Control Conference, held in Beijing. During , he served as President of the IEEE Power Electronics Society and, before that, as Program Chair and then Conference Chair of IEEE-sponsored power electronics specialist conferences.