Low-power, precision, rail-to-rail, 2.7 MHz, 16 V operational amplifier. Description

Transcription

1 Low-power, precision, rail-to-rail, 2.7 MHz, 16 V operational amplifier Datasheet - production data Features Low input offset voltage: 2 µv max. Rail-to-rail input and output Low current consumption: 8 µa max. Gain bandwidth product: 2.7 MHz Low supply voltage: V Unity gain stable Low input bias current: 5 pa max. High ESD tolerance: 4 kv HBM Extended temp. range: -4 C to +125 C Automotive qualification Related products SOT23-5 See the TSX7191 for higher speeds with similar precision See the TSX561 for low-power features See the TSX631 for micro-power features See the TSX921 for higher speeds Applications Battery-powered instrumentation Instrumentation amplifier Active filtering DAC buffer High-impedance sensor interface Current sensing (high and low side) Description The TSX711 single, operational amplifier (op amp) offers high precision functioning with low input offset voltage down to a maximum of 2 µv at 25 C. In addition, its rail-to-rail input and output functionality allows this product to be used on full range input and output without limitation. This is particularly useful for a lowvoltage supply such as 2.7 V that the TSX711 is able to operate with. Thus, the TSX711 has the great advantage of offering a large span of supply voltages, ranging from 2.7 V to 16 V. It can be used in multiple applications with a unique reference. Low input bias current performance makes the TSX711 perfect when used for signal conditioning in sensor interface applications. In addition, low-side and high-side current measurements can be easily made thanks to railto-rail functionality. High ESD tolerance (4 kv HBM) and a wide temperature range are also good arguments to use the TSX711 in the automotive market segment. July 214 DocID25959 Rev 3 1/26 This is information on a product in full production.

2 Contents TSX711 Contents 1 Package pin connections Absolute maximum ratings and operating conditions Electrical characteristics Application information Operating voltages Input pin voltage ranges Rail-to-rail input Rail-to-rail output Input offset voltage drift over temperature Long term input offset voltage drift High values of input differential voltage Capacitive load PCB layout recommendations Optimized application recommendation Application examples Oxygen sensor Low-side current sensing Package information SOT23-5 package information Ordering information Revision history /26 DocID25959 Rev 3

3 Package pin connections 1 Package pin connections Figure 1: Pin connections (top view) OUT 1 5 VCC+ IN SOT23-5 VCC- IN- DocID25959 Rev 3 3/26

4 Absolute maximum ratings and operating conditions TSX711 2 Absolute maximum ratings and operating conditions Table 1: Absolute maximum ratings (AMR) Symbol Parameter Value Unit V CC Supply voltage (1) 18 V V id Differential input voltage (2) ±V CC mv V in Input voltage V CC- -.2 to V CC++.2 V I in Input current (3) 1 ma T stg Storage temperature -65 to +15 C R thja Thermal resistance junction to ambient (4)(5) 25 C/W T j Maximum junction temperature 15 C ESD HBM: human body model (6) 4 V MM: machine model (7) 1 CDM: charged device model (8) 15 Latch-up immunity 2 ma Notes: (1) All voltage values, except the differential voltage are with respect to the network ground terminal. (2) Differential voltages are the non-inverting input terminal with respect to the inverting input terminal. See Section 4.7 for the precautions to follow when using the TSX711 with a high differential input voltage. (3) Input current must be limited by a resistor in series with the inputs. (4) Rth are typical values. (5) Short-circuits can cause excessive heating and destructive dissipation. (6) According to JEDEC standard JESD22-A114F. (7) According to JEDEC standard JESD22-A115A. (8) According to ANSI/ESD STM5.3.1 Table 2: Operating conditions Symbol Parameter Value Unit V CC Supply voltage 2.7 to 16 V V icm Common mode input voltage range V CC- -.1 to V CC+ +.1 T oper Operating free air temperature range -4 to +125 C 4/26 DocID25959 Rev 3

5 Electrical characteristics 3 Electrical characteristics Table 3: Electrical characteristics at V CC+ = +4 V with V CC- = V, V icm = V CC/2, T amb = 25 C, and RL > 1 kω connected to V CC/2 (unless otherwise specified) Symbol Parameter Conditions Min. Typ. Max. Unit V io Input offset voltage TSX711, V icm = V CC/2 2 μv T min < T op < +85 C 365 T min < T op < +125 C 45 TSX711A, V icm = V CC/2 1 T min < T op < +85 C 265 T min < T op < +125 C 35 ΔV io/δt Input offset voltage drift (1) 2.5 µv/ C ΔV io Long term input offset T = 25 C 1 voltage drift (2) nv month I ib Input bias current (1) V out = V CC/2 1 5 pa T min < T op < T max 2 I io Input offset current (1) V out = V CC/2 1 5 pa T min < T op < T max 2 R IN Input resistance 1 TΩ C IN Input capacitance 12.5 pf CMRR Common mode rejection V icm = -.1 to 4.1 V, V out = V CC/ db ratio 2 log (ΔV ic/δv io) T min < T op < T max 83 V icm = -.1 to 2 V, V out = V CC/ T min < T op < T max 94 A vd Large signal voltage gain R L= 2 kω, V out =.3 to 3.7 V db V OH High level output voltage (voltage drop from V CC+) T min < T op < T max 96 R L= 1 kω, V out =.2 to 3.8 V T min < T op < T max 96 R L= 2 kω to V CC/ mv T min < T op < T max 6 R L= 1 kω tο V CC/ T min < T op < T max 2 V OL Low level output voltage R L= 2 kω tο V CC/ mv T min < T op < T max 6 R L= 1 kω tο V CC/ T min < T op < T max 2 I out I sink V out = V CC ma T min < T op < T max 2 DocID25959 Rev 3 5/26

6 Electrical characteristics TSX711 Symbol Parameter Conditions Min. Typ. Max. Unit I out I source V out = V ma T min < T op < T max 2 I CC Supply current per amplifier No load, V out = V CC/ μa T min < T op < T max 9 GBP Gain bandwidth product R L = 1 kω, C L = 1 pf MHz ɸm Phase margin R L = 1 kω, C L = 1 pf 5 Degrees G m Gain margin R L = 1 kω, C L = 1 pf 15 db SRn Negative slew rate Av = 1, V out = 3 V PP, 1 % to 9 %.6.85 V/μs T min < T op < T max.5 SRp Positive slew rate Av = 1, V out = 3V PP, 1 % to 9 % V/μs e n Equivalent input noise voltage T min < T op < T max.9 f = 1 khz 22 f = 1 khz 19 nv Hz THD+N Total harmonic distortion + noise Notes: (1) Maximum values are guaranteed by design. f =1 khz, Av = 1, R L= 1 kω, BW = 22 khz, V in=.8 V PP.1 % (2) Typical value is based on the Vio drift observed after 1h at 125 C extrapolated to 25 C using the Arrhenius law and assuming an activation energy of.7 ev. The operational amplifier is aged in follower mode configuration (see Section 4.6). Table 4: Electrical characteristics at V CC+ = +1 V with V CC- = V, V icm = V CC/2, T amb = 25 C, and RL > 1 kω connected to V CC/2 (unless otherwise specified) Symbol Parameter Conditions Min. Typ. Max. Unit V io Input offset voltage TSX711, V icm = V CC/2 2 μv T min < T op < +85 C 365 T min < T op < +125 C 45 TSX711A, V icm = V CC/2 1 T min < T op < +85 C 265 T min < T op < +125 C 35 ΔV io/δt Input offset voltage drift (1) 2.5 μv/ C ΔV io Long term input offset T = 25 C 25 voltage drift (2) nv month I ib Input bias current (1) V out = V CC/2 1 5 pa T min < T op < T max 2 I io Input offset current (1) V out = V CC/2 1 5 pa T min < T op < T max 2 R IN Input resistance 1 TΩ 6/26 DocID25959 Rev 3

7 Electrical characteristics Symbol Parameter Conditions Min. Typ. Max. Unit C IN Input capacitance 12.5 pf CMRR Common mode rejection V icm = -.1 to 1.1 V, V out = V CC/ db ratio 2 log (ΔV ic/δv io) T min < T op < T max 86 V icm = -.1 to 8 V, V out = V CC/ T min < T op < T max 95 A vd Large signal voltage gain R L= 2 kω, V out =.3 to 9.7 V db T min < T op < T max 1 R L= 1 kω, V out =.2 to 9.8 V 11 T min < T op < T max 1 V OH High level output voltage R L= 2 kω ο V CC/ mv (voltage drop from V CC+) T min < T op < T max 8 R L= 1 kω ο V CC/2 1 3 T min < T op < T max 4 V OL Low level output voltage R L= 2 kω ο V CC/ mv T min < T op < T max 8 R L= 1 kω ο V CC/2 9 3 T min < T op < T max 4 I out I sink V out = V CC 5 7 ma T min < T op < T max 4 I source V out = V 5 69 T min < T op < T max 4 I CC Supply current per amplifier No load, V out = V CC/ μa T min < T op < T max 1 GBP Gain bandwidth product R L = 1 kω, C L = 1 pf MHz ɸm Phase margin R L = 1 kω, C L = 1 pf 53 Degrees G m Gain margin R L = 1 kω, C L = 1 pf 15 db SRn Negative slew rate Av = 1, V out = 8 V PP, 1 % to 9 %.8 1 V/μs T min < T op < T max.7 SRp Positive slew rate Av = 1, V out = 8 V PP, 1 % to 9 % V/μs e n Equivalent input noise voltage T min < T op < T max.9 f = 1 khz 22 f = 1 khz 19 nv Hz THD+N Total harmonic distortion + noise Notes: (1) Maximum values are guaranteed by design. f = 1 khz, Av = 1, R L= 1 kω, BW = 22 khz, V in= 5 V PP.3 % (2) Typical value is based on the Vio drift observed after 1h at 125 C extrapolated to 25 C using the Arrhenius law and assuming an activation energy of.7 ev. The operational amplifier is aged in follower mode configuration (see Section 4.6). DocID25959 Rev 3 7/26

8 Electrical characteristics TSX711 Table 5: Electrical characteristics at V CC+ = +16 V with V CC- = V, V icm = V CC/2, T amb = 25 C, and RL > 1 kω connected to V CC/2 (unless otherwise specified) Symbol Parameter Conditions Min. Typ. Max. Unit V io Input offset voltage TSX711, V icm = V CC/2 2 μv T min < T op < +85 C 365 T min < T op < +125 C 45 TSX711A, V icm = V CC/2 1 T min < T op < +85 C 265 T min < T op < +125 C 35 ΔV io/δt Input offset voltage drift (1) 2.5 μv/ C ΔV io Long term input offset T = 25 C 5 voltage drift (2) nv month I ib Input bias current (1) V out = V CC/2 1 5 pa T min < T op < T max 2 I io Input offset current (1) V out = V CC/2 1 5 pa T min < T op < T max 2 R IN Input resistance 1 TΩ C IN Input capacitance 12.5 pf CMRR Common mode rejection V icm = -.1 to 16.1V, V out = V CC/ db ratio 2 log (ΔV ic/δv io) T min < T op < T max 9 V icm = -.1 to 14V, V out = V CC/ T min < T op < T max 96 SVRR Supply voltage rejection V cc = 4 to 16 V db ratio 2 log (ΔV cc/δv io) T min < T op < T max 9 A vd Large signal voltage gain R L= 2 kω, V out =.3 to 15.7 V db T min < T op < T max 1 V OH High level output voltage (voltage drop from V CC+) R L= 1 kω, V out =.2 to 15.8 V T min < T op < T max 1 R L= 2 kω 1 13 mv T min < T op < T max 15 R L= 1 kω 16 4 T min < T op < T max 5 V OL Low level output voltage R L= 2 kω 4 13 mv T min < T op < T max 15 R L= 1 kω 15 4 T min < T op < T max 5 I out I sink V out = V CC 5 71 ma T min < T op < T max 45 8/26 DocID25959 Rev 3

9 Electrical characteristics Symbol Parameter Conditions Min. Typ. Max. Unit I out I source V out = V 5 68 ma T min < T op < T max 45 I CC Supply current per amplifier No load, V out = V CC/ μa T min < T op < T max 1 GBP Gain bandwidth product R L = 1 kω, C L = 1 pf MHz ɸm Phase margin R L = 1 kω, C L = 1 pf 55 Degrees G m Gain margin R L = 1 kω, C L= 1 pf 15 db SRn Negative slew rate Av = 1, V out = 1 V PP, 1 % to 9 % T min < T op < T max.6 SRp Positive slew rate Av = 1, V out = 1 V PP, 1 % to 9 % e n Equivalent input noise voltage T min < T op < T max.9 f = 1 khz 22 f = 1 khz V/μs V/μs nv Hz THD+N Total harmonic distortion + Noise Notes: (1) Maximum values are guaranteed by design. f = 1 khz, Av = 1, R L= 1 kω, BW = 22 khz, V in= 1 V PP.2 % (2) Typical value is based on the Vio drift observed after 1h at 125 C extrapolated to 25 C using the Arrhenius law and assuming an activation energy of.7 ev. The operational amplifier is aged in follower mode configuration (see Section 4.6). DocID25959 Rev 3 9/26

10 Electrical characteristics Figure 2: Supply current vs. supply voltage TSX711 Figure 3: Input offset voltage distribution at V CC = 16 V Supply Current (µa) T=125 C Vicm=Vcc/2 T=-4 C Population (%) Vicm=8V Supply Voltage (V) Input offset voltage (µv) Figure 4: Input offset voltage distribution at V CC = 4 V Figure 5: Input offset voltage vs. temperature at V CC = 16 V Population (%) Vcc=4V Vicm=2V Input offset voltage (µv) Input offset voltage (µv) Vio limit -4 Vicm=8V Temperature ( C) Figure 6: Input offset voltage drift population Figure 7: Input offset voltage vs. supply voltage at V ICM = V Population(%) Vicm=8V Vio/ T (µv/ºc) Input Offset Voltage (µv) Vicm=V T=-4 C T=125 C Supply voltage (V) 1/26 DocID25959 Rev 3

11 Figure 8: Input offset voltage vs. common mode voltage at V CC = 2.7 V Electrical characteristics Figure 9: Input offset voltage vs. common mode voltage at V CC = 16 V Vcc=2.7V 4 Input Offset Voltage (µv) T=125 C T=-4 C Input Offset Voltage (µv) T=125 C T=-4 C Input Common Mode Voltage (V) Input Common Mode Voltage (V) Figure 1: Output current vs. output voltage at V CC = 2.7 V Figure 11: Output current vs. output voltage at V CC = 16 V Output Current (ma) Sink Vid=-1V T=125 C T=-4 C -2 Source -3 Vcc=2.7V Vid=1V Output Voltage (V) Output Current (ma) 1 Sink 75 Vid=-1V T=125 C T=-4 C -75 Source -1 Vid=1V Output Voltage (V) Figure 12: Output low voltage vs. supply voltage Figure 13: Output high voltage (drop from V CC+) vs. supply voltage Output voltage (mv) Vid=-.1V Rl=1kΩ to Vcc/2 T=125 C T=-4 C Output voltage (from Vcc+) (mv) Vid=.1V Rl=1kΩ to Vcc/2 T=125 C T=-4 C Supply Voltage (V) Supply Voltage (V) DocID25959 Rev 3 11/26

12 Electrical characteristics Figure 14: Output voltage vs. input voltage close to the rail at V CC = 16 V Output voltage (V) Follower configuration Input voltage (V) Slew rate (V/µs) Figure 15: Slew rate vs. supply voltage T=125 C T=-4 C Vicm=Vcc/2 Vload=Vcc/2 Rl=1 kω Cl=1p F TSX Supply Voltage (V) Signal Amplitude (V) Figure 16: Negative slew rate at V CC = 16 V T=-4 C Vcc=16 V Vicm=Vcc/2 Rl=1 kω Cl=1pF T=125 C Time (µs) Signal Amplitude (V) Figure 17: Positive slew rate at V CC = 16 V T=-4 C T=125 C -4 Vicm=Vcc/2 Rl=1kΩ Cl=1pF Time (µs) Figure 18: Response to a small input voltage step Figure 19: Recovery behavior after a negative step on the input Signal Amplitude (V) Vicm=8V Rl=1kΩ Cl=1pF Output Voltage (V) Vin Vcc=±8V Vcc=±1.35V Gain=11 Rl=1kΩ Cl=1pF Input voltage (V) Time (µs) Time (µs) 12/26 DocID25959 Rev 3

13 Figure 2: Recovery behavior after a positive step on the input 2.4 Output Voltage (V) Vcc=±8V Vcc=±1.35V Vin Gain=11 Rl=1kΩ Cl=1pF Time (µs) Input voltage (V) Gain (db) Electrical characteristics Figure 21: Bode diagram at V CC = 2.7 V Gain T=-4 C Phase Vcc=2.7V Vicm=1.35V -18 Rl=1kΩ -1 Cl=1pF -21 Gain=11 T=125 C k 1k 1k 1M 1M Frequency (Hz) Phase ( ) Figure 22: Bode diagram at V CC = 16 V Figure 23: Power supply rejection ratio (PSRR) vs. frequency Gain (db) Gain T=-4 C Phase Vicm=8V -18 Rl=1kΩ -1 Cl=1pF -21 Gain=11 T=125 C k 1k 1k 1M 1M Frequency (Hz) Phase ( ) PSRR (db) PSRR + 6 Vicm=8V 4 Gain=1 Rl=1kΩ Cl=1pF 2 Vosc=2mV PP PSRR k 1k 1k 1M Frequency (Hz) Figure 24: Output overshoot vs. capacitive load Overshoot (%) Vicm=Vcc/2 Rl=1kΩ Vin=1mVpp Gain=1 Vcc=2.7V Cload (pf) Figure 25: Output impedance vs. frequency in closed loop configuration Output impedance (Ω) Vicm=8V Gain=1 Vosc=3mV RMS.1 1k 1k 1k 1M 1M Frequency (Hz) DocID25959 Rev 3 13/26

14 Electrical characteristics Figure 26: THD + N vs. frequency Figure 27: THD + N vs. output voltage TSX THD + N (%).1.1 1E-3 1E-4 Vicm=8V Gain=1 Vin=1Vpp BW=8kHz Rl=1kΩ Rl=1kΩ Rl=2kΩ Frequency (Hz) THD + N (%).1.1 Rl=2kΩ Rl=1kΩ Rl=1kΩ Vicm=8V 1E-3 Gain=1 f=1khz BW=22kHz 1E Output Voltage (Vpp) Figure 28: Noise vs. frequency Figure 29:.1 to 1Hz noise Equivalent Input NoiseVoltage (nv/ Hz) Vicm=Vcc/ k 1k Frequency (Hz) Input voltage noise (µv) Vicm=8V Time (s) 14/26 DocID25959 Rev 3

15 Application information 4 Application information 4.1 Operating voltages The TSX711 device can operate from 2.7 to 16 V. The parameters are fully specified for 4 V, 1 V, and 16 V power supplies. However, the parameters are very stable in the full V CC range. Additionally, the main specifications are guaranteed in extended temperature ranges from -4 to +125 C. 4.2 Input pin voltage ranges The TSX711 device has internal ESD diode protection on the inputs. These diodes are connected between the input and each supply rail to protect the input MOSFETs from electrical discharge. If the input pin voltage exceeds the power supply by.5 V, the ESD diodes become conductive and excessive current can flow through them. Without limitation this over current can damage the device. In this case, it is important to limit the current to 1 ma, by adding resistance on the input pin, as described in Figure 3: "Input current limitation". Figure 3: Input current limitation 16 V Vin R Vout 4.3 Rail-to-rail input The TSX711 device has a rail-to-rail input, and the input common mode range is extended from V CC- -.1 V to V CC+ +.1 V. 4.4 Rail-to-rail output The operational amplifier output levels can go close to the rails: to a maximum of 3 mv above and below the rail when connected to a 1 kω resistive load to V CC /2. DocID25959 Rev 3 15/26

16 Application information TSX Input offset voltage drift over temperature The maximum input voltage drift variation over temperature is defined as the offset variation related to the offset value measured at 25 C. The operational amplifier is one of the main circuits of the signal conditioning chain, and the amplifier input offset is a major contributor to the chain accuracy. The signal chain accuracy at 25 C can be compensated during production at application level. The maximum input voltage drift over temperature enables the system designer to anticipate the effect of temperature variations. The maximum input voltage drift over temperature is computed using Equation 1. Equation 1 V io T = max V io ( T) V io ( 25 C ) T 25 C Where T = -4 C and 125 C. The TSX711 datasheet maximum value is guaranteed by measurements on a representative sample size ensuring a C pk (process capability index) greater than Long term input offset voltage drift To evaluate product reliability, two types of stress acceleration are used: Voltage acceleration, by changing the applied voltage Temperature acceleration, by changing the die temperature (below the maximum junction temperature allowed by the technology) with the ambient temperature. The voltage acceleration has been defined based on JEDEC results, and is defined using Equation 2. Equation 2 Where: A FV is the voltage acceleration factor b is the voltage acceleration constant in 1/V, constant technology parameter (β = 1) V S is the stress voltage used for the accelerated test V U is the voltage used for the application The temperature acceleration is driven by the Arrhenius model, and is defined in Equation 3. Equation 3 A FV e β. ( V S V U ) = A FT = E a k T U T S e Where: A FT is the temperature acceleration factor E a is the activation energy of the technology based on the failure rate 16/26 DocID25959 Rev 3

17 k is the Boltzmann constant ( x 1-5 ev.k -1 ) T U is the temperature of the die when V U is used (K) T S is the temperature of the die under temperature stress (K) Application information The final acceleration factor, A F, is the multiplication of the voltage acceleration factor and the temperature acceleration factor (Equation 4). Equation 4 A F = A FT A FV A F is calculated using the temperature and voltage defined in the mission profile of the product. The A F value can then be used in Equation 5 to calculate the number of months of use equivalent to 1 hours of reliable stress duration. Equation 5 To evaluate the op amp reliability, a follower stress condition is used where V CC is defined as a function of the maximum operating voltage and the absolute maximum rating (as recommended by JEDEC rules). The V io drift (in µv) of the product after 1 h of stress is tracked with parameters at different measurement conditions (see Equation 6). Equation 6 Months = A F 1 h 12 months / ( 24 h days) V CC = maxv op with V icm = V CC / 2 The long term drift parameter (ΔV io ), estimating the reliability performance of the product, is obtained using the ratio of the V io (input offset voltage value) drift over the square root of the calculated number of months (Equation 7). Equation 7 V io = V io drift ( month s) Where V io drift is the measured drift value in the specified test conditions after 1 h stress duration. 4.7 High values of input differential voltage In a closed loop configuration, which represents the typical use of an op amp, the input differential voltage is low (close to V io ). However, some specific conditions can lead to higher input differential values, such as: operation in an output saturation state operation at speeds higher than the device bandwidth, with output voltage dynamics limited by slew rate. use of the amplifier in a comparator configuration, hence in open loop Use of the TSX711 in comparator configuration, especially combined with high temperature and long duration can create a permanent drift of V io. DocID25959 Rev 3 17/26

18 Application information TSX Capacitive load Driving large capacitive loads can cause stability problems. Increasing the load capacitance produces gain peaking in the frequency response, with overshoot and ringing in the step response. It is usually considered that with a gain peaking higher than 2.3 db an op amp might become unstable. Generally, the unity gain configuration is the worst case for stability and the ability to drive large capacitive loads. Figure 31: "stability criteria with a serial resistor at different supply voltage" shows the serial resistor that must be added to the output, to make a system stable. Figure 32: "Test configuration for Riso" shows the test configuration using an isolation resistor, Riso. Figure 31: stability criteria with a serial resistor at different supply voltage 1 Stable Riso (Ω) 1 Unstable Vcc=2.7V Vicm=Vcc/2 Rl=1kΩ Gain=1 1 1 p 1n 1 n 1 n Cload (F) Figure 32: Test configuration for Riso V CC+ V IN + - V CC- Riso C load VOUT 1 kω 18/26 DocID25959 Rev 3

19 Application information 4.9 PCB layout recommendations Particular attention must be paid to the layout of the PCB, tracks connected to the amplifier, load, and power supply. The power and ground traces are critical as they must provide adequate energy and grounding for all circuits. The best practice is to use short and wide PCB traces to minimize voltage drops and parasitic inductance. In addition, to minimize parasitic impedance over the entire surface, a multi-via technique that connects the bottom and top layer ground planes together in many locations is often used. The copper traces that connect the output pins to the load and supply pins should be as wide as possible to minimize trace resistance. 4.1 Optimized application recommendation It is recommended to place a 22 nf capacitor as close as possible to the supply pin. A good decoupling will help to reduce electromagnetic interference impact Application examples Oxygen sensor The electrochemical sensor creates a current proportional to the concentration of the gas being measured. This current is converted into voltage thanks to R resistance. This voltage is then amplified by TSX711 (see Figure 33: "Oxygen sensor principle schematic"). Figure 33: Oxygen sensor principle schematic R1 R2 O2_ sensor I V CC V out The output voltage is calculated using Equation 8: Equation 8 V out = ( I R V io ) R R 1 As the current delivered by the O2 sensor is extremely low, the impact of the V io can become significant with a traditional operational amplifier. The use of a precision amplifier like the TSX711 is perfect for this application. In addition, using the TSX711 for the O2 sensor application ensures that the measurement of O2 concentration is stable, even at different temperatures, thanks to a small ΔV io /ΔT. DocID25959 Rev 3 19/26

20 Application information TSX Low-side current sensing Power management mechanisms are found in most electronic systems. Current sensing is useful for protecting applications. The low-side current sensing method consists of placing a sense resistor between the load and the circuit ground. The resulting voltage drop is amplified using the TSX711 (see Figure 34: "Low-side current sensing schematic"). Figure 34: Low-side current sensing schematic C1 Rg1 Rf1 R shunt I Rg2 I n Ip V + - V out Rf2 V out can be expressed as follows: Equation 9 R g2 R g2 R f2 R f1 R g2 R f2 V ou t = R shun t I I + p 1 + l R g2 R f2 R n R f1 V io g1 R g1 Assuming that R f2 = R f1 = R f and R g2 = R g1 = R g, Equation 9 can be simplified as follows: Equation 1 R f1 R f1 R g1 R f R f V out = R shunt I V R io R g R f I io g The main advantage of using a precision amplifier like the TSX711, for a low-side current sensing, is that the errors due to V io and I io are extremely low and may be neglected. Therefore, for the same accuracy, the shunt resistor can be chosen with a lower value, resulting in lower power dissipation, lower drop in the ground path, and lower cost. Particular attention must be paid on the matching and precision of R g1, R g2, R f1, and R f2, to maximize the accuracy of the measurement. Taking into consideration the resistor inaccuracies, the maximum and minimum output voltage of the operational amplifier can be calculated respectively using Equation 11 and Equation 12. 2/26 DocID25959 Rev 3

21 Application information Equation 11 Rf Rf Maximum Vout = Rshunt I ( 1 + ε rs + 2ε r) + Vi o 1 + Rg Rg + Rf lio Equation 12 Rf Rf Minimum Vout = Rshunt I ( 1 ε rs 2ε r ) Vi o 1 + Rg Rg + Rf lio Where: εrs is the shunt resistor inaccuracy (example, 1 % ) εr is the inaccuracy of the Rf and Rg resistors (example,.1 %) DocID25959 Rev 3 21/26

22 Package information TSX711 5 Package information In order to meet environmental requirements, ST offers these devices in different grades of ECOPACK packages, depending on their level of environmental compliance. ECOPACK specifications, grade definitions and product status are available at: ECOPACK is an ST trademark. 22/26 DocID25959 Rev 3

23 Package information 5.1 SOT23-5 package information Figure 35: SOT23-5 package mechanical drawing Table 6: SOT23-5 package mechanical data Ref. Dimensions Millimeters Inches Min. Typ. Max. Min. Typ. Max. A A A B C D D e E F L K degrees 1 degrees degrees 1 degrees DocID25959 Rev 3 23/26

24 Ordering information TSX711 6 Ordering information Order code Temperature range Table 7: Order codes Package Packaging Marking TSX711ILT -4 to +125 C SΟΤ23-5 Tape and reel K29 TSX711AILT TSX711IYLT (1) TSX711AIYLT (1) K195 K197 K198 Notes: (1) Qualification and characterization according to AEC Q1 and Q3 or equivalent, advanced screening according to AEC Q1 & Q 2 or equivalent are on-going. 24/26 DocID25959 Rev 3

25 Revision history 7 Revision history Table 8: Document revision history Date Revision Changes 27-Feb Initial release 19-Mar Table 1: updated ESD data for MM (machine model) 25-Jul Table 3: updated I out (I sink) values. Table 3, Table 4, and Table 5: updated V io values, updated ΔV io/δt. Table 5 : updated V OL values Table 7: updated inches dimensions DocID25959 Rev 3 25/26

26 IMPORTANT NOTICE PLEASE READ CAREFULLY STMicroelectronics NV and its subsidiaries ( ST ) reserve the right to make changes, corrections, enhancements, modifications, and improvements to ST products and/or to this document at any time without notice. Purchasers should obtain the latest relevant information on ST products before placing orders. ST products are sold pursuant to ST s terms and conditions of sale in place at the time of order acknowledgement. Purchasers are solely responsible for the choice, selection, and use of ST products and ST assumes no liability for application assistance or the design of Purchasers products. No license, express or implied, to any intellectual property right is granted by ST herein. Resale of ST products with provisions different from the information set forth herein shall void any warranty granted by ST for such product. ST and the ST logo are trademarks of ST. All other product or service names are the property of their respective owners. Information in this document supersedes and replaces information previously supplied in any prior versions of this document. 214 STMicroelectronics All rights reserved 26/26 DocID25959 Rev 3

27 Mouser Electronics Authorized Distributor Click to View Pricing, Inventory, Delivery & Lifecycle Information: STMicroelectronics: TSX711ILT TSX711AILT