General-Purpose CMOS Rail-to-Rail Amplifiers FEATURES Single-supply operation: 2.7 V to 5.5 V Low supply current: 45 μa/amplifier Wide bandwidth: MHz No phase reversal Low input currents: 4 pa Unity gain stable Rail-to-rail input and output PIN CONFIGURATIONS OUT A V +IN A 2 3 AD854 5 V+ 4 IN A Figure. 5-Lead SC7 and 5-Lead SOT-23 (KS and RJ Suffixes) 935- APPLICATIONS ASIC input or output amplifiers Sensor interfaces Piezoelectric transducer amplifiers Medical instrumentation Mobile communications Audio outputs Portable systems NC IN A +IN A V 2 3 4 AD854 8 7 6 5 NC V+ OUT A NC NC = NO CONNECT Figure 2. 8-Lead SOIC (R Suffix) 935-2 GENERAL DESCRIPTION The are single, dual, and quad railto-rail input and output, single-supply amplifiers featuring very low supply current and MHz bandwidth. All are guaranteed to operate from a 2.7 V single supply as well as a 5 V supply. These parts provide MHz bandwidth at a low current consumption of 45 μa per amplifier. Very low input bias currents enable the to be used for integrators, photodiode amplifiers, piezoelectric sensors, and other applications with high source impedance. The supply current is only 45 μa per amplifier, ideal for battery operation. Rail-to-rail inputs and outputs are useful to designers buffering ASICs in single-supply systems. The are optimized to maintain high gains at lower supply voltages, making them useful for active filters and gain stages. The are specified over the extended industrial temperature range ( C to +25 C). The AD854 is available in 5-lead SOT-23, 5-lead SC7, and 8-lead SOIC packages. The AD8542 is available in 8-lead SOIC, 8-lead MSOP, and 8-lead TSSOP surface-mount packages. The AD8544 is available in 4-lead narrow SOIC and 4-lead TSSOP surfacemount packages. All MSOP, SC7, and SOT versions are available in tape and reel only. OUT A IN A +IN A 2 3 AD8542 V 4 5 +IN B 8 7 6 V+ OUT B IN B Figure 3. 8-Lead SOIC, 8-Lead MSOP, and 8-Lead TSSOP (R, RM, and RU Suffixes) OUT A IN A +IN A 2 3 AD8544 4 3 2 V+ 4 V +IN B IN B OUT B 5 6 7 9 8 OUT D IN D +IN D +IN C IN C OUT C Figure 4. 4-Lead SOIC and 4-Lead TSSOP (R and RU Suffixes) 935-3 935-4 Rev. F Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. Specifications subject to change without notice. No license is granted by implication or otherwise under any patent or patent rights of Analog Devices. Trademarks and registered trademarks are the property of their respective owners. One Technology Way, P.O. Box 96, Norwood, MA 62-96, U.S.A. Tel: 78.329.47 www.analog.com Fax: 78.46.33 8 Analog Devices, Inc. All rights reserved.
TABLE OF CONTENTS Features... Applications... General Description... Pin Configurations... Revision History... 2 Specifications... 3 Electrical Characteristics... 3 Absolute Maximum Ratings... 6 Thermal Resistance... 6 ESD Caution... 6 Typical Performance Characteristics...7 Theory of Operation... 3 Notes on the AD854x Amplifiers... 3 Applications... 4 Notch Filter... 4 Comparator Function... 4 Photodiode Application... 5 Outline Dimensions... 6 Ordering Guide... 8 REVISION HISTORY /8 Rev. E to Rev. F Inserted Figure 2; Renumbered Sequentially... 9 Changes to Figure 22 Caption... 9 Changes to Notch Filter Section, Figure 35, Figure 36, and Figure 37... 3 Updated Outline Dimensions... 6 /7 Rev. D to Rev. E Updated Format...Universal Changes to Photodiode Application Section... 4 Changes to Ordering Guide... 7 8/4 Rev. C to Rev. D Changes to Ordering Guide...5 Changes to Figure 3... Updated Outline Dimensions... 2 /3 Rev. B to Rev. C Updated Format...Universal Changes to General Description... Changes to Ordering Guide...5 Changes to Outline Dimensions... 2 Rev. F Page 2 of
SPECIFICATIONS ELECTRICAL CHARACTERISTICS VS = 2.7 V, VCM =.35 V, TA = 25 C, unless otherwise noted. Table. Parameter Symbol Conditions Min Typ Max Unit INPUT CHARACTERISTICS Offset Voltage VOS 6 mv C TA +25 C 7 mv Input Bias Current IB 4 pa C TA +85 C pa C TA +25 C pa Input Offset Current IOS. 3 pa C TA +85 C 5 pa C TA +25 C 5 pa Input Voltage Range 2.7 V Common-Mode Rejection Ratio CMRR VCM = V to 2.7 V 45 db C TA +25 C 38 db Large Signal Voltage Gain AVO RL = kω, VO =.5 V to 2.2 V 5 V/mV C TA +85 C 5 V/mV C TA +25 C 2 V/mV Offset Voltage Drift ΔVOS/ΔT C TA +25 C 4 μv/ C Bias Current Drift ΔIB/ΔT C TA +85 C fa/ C C TA +25 C fa/ C Offset Current Drift ΔIOS/ΔT C TA +25 C 25 fa/ C OUTPUT CHARACTERISTICS Output Voltage High VOH IL = ma 2.575 2.65 V C TA +25 C 2.55 V Output Voltage Low VOL IL = ma 35 mv C TA +25 C 25 mv Output Current IOUT VOUT = VS V 5 ma ISC ± ma Closed-Loop Output Impedance ZOUT f = khz, AV = 5 Ω POWER SUPPLY Power Supply Rejection Ratio PSRR VS = 2.5 V to 6 V 65 76 db C TA +25 C db Supply Current/Amplifier ISY VO = V 38 55 μa C TA +25 C 75 μa DYNAMIC PERFORMANCE Slew Rate SR RL = kω.4.75 V/μs Settling Time ts To.% ( V step) 5 μs Gain Bandwidth Product GBP 98 khz Phase Margin 63 Degrees NOISE PERFORMANCE ΦM Voltage Noise Density en f = khz nv/ Hz en f = khz 38 nv/ Hz Current Noise Density in <. pa/ Hz Rev. F Page 3 of
VS = 3. V, VCM =.5 V, TA = 25 C, unless otherwise noted. Table 2. Parameter Symbol Conditions Min Typ Max Unit INPUT CHARACTERISTICS Offset Voltage VOS 6 mv C TA +25 C 7 mv Input Bias Current IB 4 pa C TA +85 C pa C TA +25 C pa Input Offset Current IOS. 3 pa C TA +85 C 5 pa C TA +25 C 5 pa Input Voltage Range 3 V Common-Mode Rejection Ratio CMRR VCM = V to 3 V 45 db C TA +25 C 38 db Large Signal Voltage Gain AVO RL = kω, VO =.5 V to 2.2 V 5 V/mV C TA +85 C 5 V/mV C TA +25 C 2 V/mV Offset Voltage Drift ΔVOS/ΔT C TA +25 C 4 μv/ C Bias Current Drift ΔIB/ΔT C TA +85 C fa/ C C TA +25 C fa/ C Offset Current Drift ΔIOS/ΔT C TA +25 C 25 fa/ C OUTPUT CHARACTERISTICS Output Voltage High VOH IL = ma 2.875 2.955 V C TA +25 C 2.85 V Output Voltage Low VOL IL = ma 32 mv C TA +25 C 25 mv Output Current IOUT VOUT = VS V 8 ma ISC ±25 ma Closed-Loop Output Impedance ZOUT f = khz, AV = 5 Ω POWER SUPPLY Power Supply Rejection Ratio PSRR VS = 2.5 V to 6 V 65 76 db C TA +25 C db Supply Current/Amplifier ISY VO = V μa C TA +25 C 75 μa DYNAMIC PERFORMANCE Slew Rate SR RL = kω.4.8 V/μs Settling Time ts To.% ( V step) 5 μs Gain Bandwidth Product GBP 98 khz Phase Margin ΦM 64 Degrees NOISE PERFORMANCE Voltage Noise Density en f = khz 42 nv/ Hz en f = khz 38 nv/ Hz Current Noise Density in <. pa/ Hz Rev. F Page 4 of
VS = 5. V, VCM = 2.5 V, TA = 25 C, unless otherwise noted. Table 3. Parameter Symbol Conditions Min Typ Max Unit INPUT CHARACTERISTICS Offset Voltage VOS 6 mv C TA +25 C 7 mv Input Bias Current IB 4 pa C TA +85 C pa C TA +25 C pa Input Offset Current IOS. 3 pa C TA +85 C 5 pa C TA +25 C 5 pa Input Voltage Range 5 V Common-Mode Rejection Ratio CMRR VCM = V to 5 V 48 db C TA +25 C 38 db Large Signal Voltage Gain AVO RL = kω, VO =.5 V to 2.2 V V/mV C TA +85 C V/mV C TA +25 C 2 V/mV Offset Voltage Drift ΔVOS/ΔT C TA +25 C 4 μv/ C Bias Current Drift ΔIB/ΔT C TA +85 C fa/ C C TA +25 C fa/ C Offset Current Drift ΔIOS/ΔT C TA +25 C 25 fa/ C OUTPUT CHARACTERISTICS Output Voltage High VOH IL = ma 4.9 4.965 V C TA +25 C 4.875 V Output Voltage Low VOL IL = ma 25 mv C TA +25 C 25 mv Output Current IOUT VOUT = VS V 3 ma ISC ± ma Closed-Loop Output Impedance ZOUT f = khz, AV = 45 Ω POWER SUPPLY Power Supply Rejection Ratio PSRR VS = 2.5 V to 6 V 65 76 db C TA +25 C db Supply Current/Amplifier ISY VO = V 45 65 μa C TA +25 C 85 μa DYNAMIC PERFORMANCE Slew Rate SR RL = kω, CL = pf.45.92 V/μs Full Power Bandwidth BWP % distortion 7 khz Settling Time ts To.% ( V step) 6 μs Gain Bandwidth Product GBP khz Phase Margin ΦM 67 Degrees NOISE PERFORMANCE Voltage Noise Density en f = khz 42 nv/ Hz en f = khz 38 nv/ Hz Current Noise Density in <. pa/ Hz Rev. F Page 5 of
ABSOLUTE MAXIMUM RATINGS Table 4. Parameter Rating Supply Voltage (VS) 6 V Input Voltage GND to VS Differential Input Voltage ±6 V Storage Temperature Range 65 C to +5 C Operating Temperature Range C to +25 C Junction Temperature Range 65 C to +5 C Lead Temperature (Soldering, sec) 3 C For supplies less than 6 V, the differential input voltage is equal to ±VS. Stresses above those listed under Absolute Maximum Ratings may cause permanent damage to the device. This is a stress rating only; functional operation of the device at these or any other conditions above those indicated in the operational section of this specification is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability. THERMAL RESISTANCE θja is specified for the worst-case conditions, that is, a device soldered in a circuit board for surface-mount packages. Table 5. Package Type θja θjc Unit 5-Lead SC7 (KS) 376 26 C/W 5-Lead SOT-23 (RJ) 23 46 C/W 8-Lead SOIC (R) 58 43 C/W 8-Lead MSOP (RM) 45 C/W 8-Lead TSSOP (RU) 2 43 C/W 4-Lead SOIC (R) 36 C/W 4-Lead TSSOP (RU) 2 43 C/W ESD CAUTION Rev. F Page 6 of
TYPICAL PERFORMANCE CHARACTERISTICS NUMBER OF AMPLIFIERS 8 8 V S =5V V CM =2.5V INPUT BIAS CURRENT (pa) 35 3 25 5 5 V S = 2.7V AND 5V V CM = V S /2 4.5 3.5 2.5.5.5.5.5 2.5 3.5 4.5 INPUT OFFSET VOLTAGE (mv) Figure 5. Input Offset Voltage Distribution 935-5 8 TEMPERATURE ( C) Figure 8. Input Bias Current vs. Temperature 935-8..5 V S = 2.7V AND 5V V CM = V S /2 7 6 V S = 2.7V AND 5V V CM = V S /2 INPUT OFFSET VOLTAGE (mv).5..5 2. 2.5 3. INPUT OFFSET CURRENT (pa) 5 4 3 2 3.5 4. 55 35 5 5 25 45 65 85 5 25 TEMPERATURE ( C) Figure 6. Input Offset Voltage vs. Temperature 45 935-6 55 35 5 5 25 45 65 85 5 25 45 TEMPERATURE ( C) Figure 9. Input Offset Current vs. Temperature 935-9 9 8 V S = 2.7V AND 5V V CM = V S /2 V S = 2.7V INPUT BIAS CURRENT (pa) 7 6 5 4 3 2 POWER SUPPLY REJECTION (db) 8 +PSRR PSRR.5.5.5 2.5 3.5 4.5 5.5 COMMON-MODE VOLTAGE (V) Figure 7. Input Bias Current vs. Common-Mode Voltage 935-7 k k k M M FREQUENCY (Hz) Figure. Power Supply Rejection vs. Frequency 935- Rev. F Page 7 of
Δ OUTPUT VOLTAGE (mv) k k. V S = 2.7V SOURCE SINK SMALL SIGNAL OVERSHOOT (%) 5 3 V S = 2.7V R L = kω +OS OS.... LOAD CURRENT (ma) Figure. Output Voltage to Supply Rail vs. Load Current 935- k k CAPACITANCE (pf) Figure 4. Small Signal Overshoot vs. Load Capacitance 935-4 OUTPUT SWING (V p-p) 3. 2.5 2..5..5 V S = 2.7V V IN = 2.5V p-p R L = 2kΩ SMALL SIGNAL OVERSHOOT (%) 5 3 V S = 2.7V R L = 2kΩ +OS OS k k k M M FREQUENCY (Hz) Figure 2. Closed-Loop Output Voltage Swing vs. Frequency 935-2 k k CAPACITANCE (pf) Figure 5. Small Signal Overshoot vs. Load Capacitance 935-5 SMALL SIGNAL OVERSHOOT (%) 5 3 V S = 2.7V R L = +OS OS.35V V S = 2.7V R L = kω C L = 3pF A V = k k CAPACITANCE (pf) Figure 3. Small Signal Overshoot vs. Load Capacitance 935-3 5mV µs Figure 6. Small Signal Transient Response 935-6 Rev. F Page 8 of
.35V V S = 2.7V R L = 2kΩ A V = COMMON-MODE REJECTION (db) 9 8 7 5 3 5mV µs Figure 7. Large Signal Transient Response 935-7 k k k M M FREQUENCY (Hz) Figure. Common-Mode Rejection vs. Frequency 935- GAIN (db) 8 V S = 2.7V R L = NO LOAD 45 9 35 8 PHASE SHIFT (Degrees) INPUT OFFSET VOLTAGE (mv) 5 4 3 2 2 3 V S =5V R L = NO LOAD T A =25 C k k k M M FREQUENCY (Hz) Figure 8. Open-Loop Gain and Phase vs. Frequency 935-8 4 5.5..5 2. 2.5 3. 3.5 4. 4.5 5. COMMON-MODE VOLTAGE (V) Figure 2. Input Offset Voltage vs. Common-Mode Voltage 935- POWER SUPPLY REJECTION RATIO (db) 8 +PSRR PSRR Δ OUTPUT VOLTAGE (mv) k k. SOURCE SINK k k k M M FREQUENCY (Hz) Figure 9. Power Supply Rejection Ratio vs. Frequency 935-9.... LOAD CURRENT (ma) Figure 22. Output Voltage to Supply Rail vs. Load Current 935-2 Rev. F Page 9 of
OUTPUT SWING (V p-p) 5. 4.5 4. 3.5 3. 2.5 2..5..5 V IN = 4.9V p-p R L = NO LOAD SMALL SIGNAL OVERSHOOT (%) 5 3 R L = 2kΩ +OS OS k k k M M FREQUENCY (Hz) Figure 23. Closed-Loop Output Voltage Swing vs. Frequency, 935-22 k k CAPACITANCE (pf) Figure 26. Small Signal Overshoot vs. Load Capacitance 935-25 OUTPUT SWING (V p-p) 5. 4.5 4. 3.5 3. 2.5 2..5..5 V IN = 4.9V p-p R L = 2kΩ SMALL SIGNAL OVERSHOOT (%) 5 3 R L = +OS OS k k k M M FREQUENCY (Hz) Figure 24. Closed-Loop Output Voltage Swing vs. Frequency 935-23 k k CAPACITANCE (pf) Figure 27. Small Signal Overshoot vs. Load Capacitance 935-26 SMALL SIGNAL OVERSHOOT (%) 5 3 R L = kω +OS OS k k CAPACITANCE (pf) Figure 25. Small Signal Overshoot vs. Load Capacitance 935-24 2.5V R L = kω C L = 3pF A V = 5mV µs Figure 28. Small Signal Transient Response 935-27 Rev. F Page of
R L = 2kΩ A V = V IN R L = kω A V = V OUT 2.5V 2.5V V µs 935-28 V µs 935-3 Figure 29. Large Signal Transient Response Figure 3. No Phase Reversal GAIN (db) 8 R L = NO LOAD 45 9 35 8 PHASE SHIFT (Degrees) SUPPLY CURRENT/AMPLIFIER (µa) 5 3 k k k M M FREQUENCY (Hz) Figure 3. Open-Loop Gain and Phase vs. Frequency 935-29 2 3 4 5 6 SUPPLY VOLTAGE (V) Figure 32. Supply Current per Amplifier vs. Supply Voltage 935-3 Rev. F Page of
SUPPLY CURRENT/AMPLIFIER (µa) 55 5 45 35 3 25 V S = 2.7V 5nV/DIV V S =5V MARKER SET @ khz MARKER READING: 37.6nV/ Hz 55 35 5 5 25 45 65 85 5 25 45 TEMPERATURE ( C) Figure 33. Supply Current per Amplifier vs. Temperature 935-32 5 5 25 FREQUENCY (khz) Figure 35. Voltage Noise 935-34 9 8 V S = 2.7V AND 5V A V = T A =25 C 7 IMPEDANCE (Ω) 5 3 k k k M M M FREQUENCY (Hz) Figure 34. Closed-Loop Output Impedance vs. Frequency 935-33 Rev. F Page 2 of
THEORY OF OPERATION NOTES ON THE AD854X AMPLIFIERS The amplifiers are improved performance, general-purpose operational amplifiers. Performance has been improved over previous amplifiers in several ways, including lower supply current for MHz gain bandwidth, higher output current, and better performance at lower voltages. Lower Supply Current for MHz Gain Bandwidth The AD854x series typically uses 45 μa of current per amplifier, which is much less than the μa to 7 μa used in earlier generation parts with similar performance. This makes the AD854x series a good choice for upgrading portable designs for longer battery life. Alternatively, additional functions and performance can be added at the same current drain. Higher Output Current At 5 V single supply, the short-circuit current is typically μa. Even V from the supply rail, the AD854x amplifiers can provide a 3 ma output current, sourcing, or sinking. Sourcing and sinking are strong at lower voltages, with 5 ma available at 2.7 V and 8 ma at 3. V. For even higher output currents, see the AD853/AD8532/AD8534 parts for output currents to 25 ma. Information on these parts is available from your Analog Devices, Inc. representative, and data sheets are available at www.analog.com. Better Performance at Lower Voltages The AD854x family of parts was designed to provide better ac performance at 3. V and 2.7 V than previously available parts. Typical gain bandwidth product is close to MHz at 2.7 V. Voltage gain at 2.7 V and 3. V is typically 5,. Phase margin is typically over C, making the part easy to use. Rev. F Page 3 of
APPLICATIONS NOTCH FILTER The AD854x have very high open-loop gain (especially with a supply voltage below 4 V), which makes it useful for active filters of all types. For example, Figure 36 illustrates the AD8542 in the classic twin-t notch filter design. The twin-t notch is desired for simplicity, low output impedance, and minimal use of op amps. In fact, this notch filter can be designed with only one op amp if Q adjustment is not required. Simply remove U2 as illustrated in Figure 37. However, a major drawback to this circuit topology is ensuring that all the Rs and Cs closely match. The components must closely match or notch frequency offset and drift causes the circuit to no longer attenuate at the ideal notch frequency. To achieve desired performance, % or better component tolerances or special component screens are usually required. One method to desensitize the circuit-to-component mismatch is to increase R2 with respect to R, which lowers Q. A lower Q increases attenuation over a wider frequency range but reduces attenuation at the peak notch frequency. V IN V IN R kω 2C 53.6µF R kω 2.5V REF R/2 5kΩ C 26.7nF f = 2πRC f = R 4 R + R2 2.5V REF C 26.7nF 5.V 3 8 /2 AD8542 U 2 4 V IN /2 AD8542 5 7 U2 6 Figure 36. Hz Twin-T Notch Filter, Q = R R 3 7 AD854 U 2 2C 4 6 R/2 5.V R2 2.5kΩ V OUT R 97.5kΩ 2.5V REF C C Figure 37. Hz Twin-T Notch Filter, Q = (Ideal) V OUT 935-35 935-36 Figure 38 is an example of the AD8544 in a notch filter circuit. The frequency dependent negative resistance (FDNR) notch filter has fewer critical matching requirements than the twin-t notch, where as the Q of the FDNR is directly proportional to a single resistor R. Although matching component values is still important, it is also much easier and/or less expensive to accomplish in the FDNR circuit. For example, the twin-t notch uses three capacitors with two unique values, whereas the FDNR circuit uses only two capacitors, which may be of the same value. U3 is simply a buffer that is added to lower the output impedance of the circuit. V IN 2.5V REF /4 AD8544 7 U2 f = 2π LC L = R 2 C2 R Q ADJUST Ω 6 5 C µf C2 µf 9 R 2.6kΩ R 2.6kΩ R 2.6kΩ R 2.6kΩ 2.5V REF /4 AD8544 U3 8 3 4 /4 AD8544 U 2 3 2 /4 AD8544 U4 4 V OUT 2.5V REF Figure 38. FDNR Hz Notch Filter with Output Buffer COMPARATOR FUNCTION A comparator function is a common application for a spare op amp in a quad package. Figure 39 illustrates ¼ of the AD8544 as a comparator in a standard overload detection application. Unlike many op amps, the AD854x family can double as comparators because this op amp family has a rail-to-rail differential input range, rail-to-rail output, and a great speed vs. power ratio. R2 is used to introduce hysteresis. The AD854x, when used as comparators, have 5 μs propagation delay at 5 V and 5 μs overload recovery time. V IN 2.5V REF R kω 2.5V DC R2 MΩ /4 AD854 V OUT Figure 39. AD854x Comparator Application Overload Detector 935-38 NC 935-37 Rev. F Page 4 of
PHOTODIODE APPLICATION The AD854x family has very high impedance with an input bias current typically around 4 pa. This characteristic allows the AD854x op amps to be used in photodiode applications and other applications that require high input impedance. Note that the AD854x has significant voltage offset that can be removed by capacitive coupling or software calibration. Figure illustrates a photodiode or current measurement application. The feedback resistor is limited to MΩ to avoid excessive output offset. In addition, a resistor is not needed on the noninverting input to cancel bias current offset because the bias current-related output offset is not significant when compared to the voltage offset contribution. For best performance, follow the standard high impedance layout techniques, which include the following: Shielding the circuit. Cleaning the circuit board. Putting a trace connected to the noninverting input around the inverting input. Using separate analog and digital power supplies. OR 2.5V REF D 2.5V REF 2 3 C pf R MΩ V+ 7 6 4 AD854 V OUT Figure. High Input Impedance Application Photodiode Amplifier 935-39 Rev. F Page 5 of
OUTLINE DIMENSIONS. BSC 2.8 BSC.3.5.9.5 MAX PIN 5 2.9 BSC 2 3.9 BSC 4.5.3.95 BSC.45 MAX SEATING PLANE.22.8 COMPLIANT TO JEDEC STANDARDS MO-78-AA Figure 4. 5-Lead Small Outline Transistor Package [SOT-23] (RJ-5) Dimensions shown in millimeters 5..45.3.5..8 4.5 4. 4.3 PIN 4 8.5.5.65 BSC 5. 5. 4.9.3.9 7 6. BSC. MAX SEATING PLANE..9 COPLANARITY. 8 COMPLIANT TO JEDEC STANDARDS MO-53-AB- Figure 42. 4-Lead Thin Shrink Small Outline Package [TSSOP] (RU-4) Dimensions shown in millimeters.75..45 2. 2..8 8.75 (.3445) 8.55 (.3366).35.25.5 5 4 2 3 2. 2..8 4. (.575) 3.8 (.496) 4 8 7 6. (.244) 5.8 (.2283)..9.7. MAX PIN.3.5. COPLANARITY.65 BSC..8 SEATING PLANE...22.8 COMPLIANT TO JEDEC STANDARDS MO-3-AA.46.36.26 Figure 43. 5-Lead Thin Shrink Small Outline Transistor Package [SC7] (KS-5) Dimensions shown in millimeters.25 (.98). (.39) COPLANARITY..27 (.5) BSC.5 (.).3 (.22).75 (.689).35 (.53) SEATING PLANE.25 (.98).7 (.67).5 (.97).25 (.98).27 (.5). (.57) COMPLIANT TO JEDEC STANDARDS MS-2-AB CONTROLLING DIMENSIONS ARE IN MILLIMETERS; INCH DIMENSIONS (IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN. Figure 44. 4-Lead Standard Small Outline Package [SOIC_N] Narrow Body (R-4) Dimensions shown in millimeters and (inches) 8 45 6-A Rev. F Page 6 of
3. 3. 2.8 3. 3. 2.9 3. 3. 2.8 8 5 4 5.5 4.9 4.65 8 5 4.5 4. 4.3 6. BSC.95.85.75.5. PIN.65 BSC.38.22 COPLANARITY.. MAX SEATING PLANE.23.8.8.. COMPLIANT TO JEDEC STANDARDS MO-87-AA Figure 45. 8-Lead Mini Small Outline Package [MSOP] (RM-8) Dimensions shown in millimeters 5. (.968) 4.8 (.89) 8.5.5 PIN COPLANARITY. 4.65 BSC.3.9. MAX SEATING PLANE..9 8 COMPLIANT TO JEDEC STANDARDS MO-53-AA.75..45 Figure 46. 8-Lead Thin Shrink Small Outline Package [TSSOP] (RU-8) Dimensions shown in millimeters 4. (.574) 3.8 (.497) 8 5 4 6. (.244) 5.8 (.2284).25 (.98). (.) COPLANARITY. SEATING PLANE.27 (.5) BSC.75 (.688).35 (.532).5 (.).3 (.22) 8.25 (.98).7 (.67).5 (.96).25 (.99).27 (.5). (.57) 45 COMPLIANT TO JEDEC STANDARDS MS-2-AA CONTROLLING DIMENSIONS ARE IN MILLIMETERS; INCH DIMENSIONS (IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN. Figure 47. 8-Lead Standard Small Outline Package [SOIC_N] Narrow Body (R-8) Dimensions shown in millimeters and (inches) 27-A Rev. F Page 7 of
ORDERING GUIDE Model Temperature Range Package Description Package Option Branding AD854AKS-R2 C to +25 C 5-Lead SC7 KS-5 A4B AD854AKS-REEL7 C to +25 C 5-Lead SC7 KS-5 A4B AD854AKSZ-R2 C to +25 C 5-Lead SC7 KS-5 A2 AD854AKSZ-REEL7 C to +25 C 5-Lead SC7 KS-5 A2 AD854ART-R2 C to +25 C 5-Lead SOT-23 RJ-5 A4A AD854ART-REEL C to +25 C 5-Lead SOT-23 RJ-5 A4A AD854ART-REEL7 C to +25 C 5-Lead SOT-23 RJ-5 A4A AD854ARTZ-R2 C to +25 C 5-Lead SOT-23 RJ-5 A4A# AD854ARTZ-REEL C to +25 C 5-Lead SOT-23 RJ-5 A4A# AD854ARTZ-REEL7 C to +25 C 5-Lead SOT-23 RJ-5 A4A# AD854AR C to +25 C 8-Lead SOIC_N R-8 AD854AR-REEL C to +25 C 8-Lead SOIC_N R-8 AD854AR-REEL7 C to +25 C 8-Lead SOIC_N R-8 AD854ARZ C to +25 C 8-Lead SOIC_N R-8 AD854ARZ-REEL C to +25 C 8-Lead SOIC_N R-8 AD854ARZ-REEL7 C to +25 C 8-Lead SOIC_N R-8 AD8542AR C to +25 C 8-Lead SOIC_N R-8 AD8542AR-REEL C to +25 C 8-Lead SOIC_N R-8 AD8542AR-REEL7 C to +25 C 8-Lead SOIC_N R-8 AD8542ARZ C to +25 C 8-Lead SOIC_N R-8 AD8542ARZ-REEL C to +25 C 8-Lead SOIC_N R-8 AD8542ARZ-REEL7 C to +25 C 8-Lead SOIC_N R-8 AD8542ARM-R2 C to +25 C 8-Lead MSOP RM-8 AVA AD8542ARM-REEL C to +25 C 8-Lead MSOP RM-8 AVA AD8542ARMZ-R2 C to +25 C 8-Lead MSOP RM-8 AVA# AD8542ARMZ-REEL C to +25 C 8-Lead MSOP RM-8 AVA# AD8542ARU C to +25 C 8-Lead TSSOP RU-8 AD8542ARU-REEL C to +25 C 8-Lead TSSOP RU-8 AD8542ARUZ C to +25 C 8-Lead TSSOP RU-8 AD8542ARUZ-REEL C to +25 C 8-Lead TSSOP RU-8 AD8544AR C to +25 C 4-Lead SOIC_N R-4 AD8544AR-REEL C to +25 C 4-Lead SOIC_N R-4 AD8544AR-REEL7 C to +25 C 4-Lead SOIC_N R-4 AD8544ARZ C to +25 C 4-Lead SOIC_N R-4 AD8544ARZ-REEL C to +25 C 4-Lead SOIC_N R-4 AD8544ARZ-REEL7 C to +25 C 4-Lead SOIC_N R-4 AD8544ARU C to +25 C 4-Lead TSSOP RU-4 AD8544ARU-REEL C to +25 C 4-Lead TSSOP RU-4 AD8544ARUZ C to +25 C 4-Lead TSSOP RU-4 AD8544ARUZ-REEL C to +25 C 4-Lead TSSOP RU-4 Z = RoHS Compliant Part; # denotes RoHS compliant product may be top or bottom marked. Rev. F Page 8 of
NOTES Rev. F Page 9 of
NOTES 8 Analog Devices, Inc. All rights reserved. Trademarks and registered trademarks are the property of their respective owners. D935--/8(F) Rev. F Page of