Low-Cost, 230MHz, Single/Quad Op Amps with Rail-to-Rail Outputs and ±15kV ESD Protection OUT

Transcription

1 9-4; Rev ; 9/5 Low-Cost, 3MHz, Single/Quad Op Amps with General Description The op amps are unity-gain stable devices that combine high-speed performance, rail-to-rail outputs, and ±5kV ESD protection. Targeted for applications where an input or an output is exposed to the outside world, such as video and communications, these devices are compliant with International ESD Standards: ±5kV IEC -4- Air-Gap Discharge, ±8kV IEC -4- Contact Discharge, and the ±5kV Human Body Model. The operate from a single 5V supply with a common-mode input voltage range that extends beyond V EE. The consume only 5.5mA of quiescent supply current per amplifier while achieving a 3MHz -3dB bandwidth, 3MHz.dB gain flatness and a 45V/µs slew rate. Set-Top Boxes Surveillance Video Systems Battery-Powered Instruments Analog-to-Digital Converter Interface Applications CCD Imaging Systems Video Routing and Switching Systems Digital Cameras Video-on-Demand Video Line Driver Features ESD-Protected Inputs and Outputs ±5kV Human Body Model ±8kV IEC -4- Contact Discharge ±5kV IEC -4- Air-Gap Discharge Low Cost and High Speed 3MHz -3dB Bandwidth 3MHz.dB Gain Flatness 45V/µs Slew Rate Rail-to-Rail Outputs Input Common-Mode Range Extends Beyond V EE Low Differential Gain/Phase:.%/. Low Distortion at 5MHz -6dBc SFDR -58dB Total Harmonic Distortion Ultra-Small 5-Pin SOT3 and 4-Pin TSSOP Packages PART Ordering Information TEMP RANGE IN- PIN- PACKAGE TOP MARK MAX4385EEUK-T -4 C to +85 C 5 SOT3-5 ADZL MAX4386EESD -4 C to +85 C 4 SO MAX4386EEUD -4 C to +85 C 4 TSSOP Typical Operating Circuit Pin Configurations 5V IN 75Ω MAX4385E.µF 75Ω Z o = 75Ω OUT TOP VIEW OUT V EE 5 V CC MAX4385E 75Ω IN+ 3 4 Ω Ω SOT3 VIDEO LINE DRIVER Pin Configurations continued at end of data sheet. Maxim Integrated Products For pricing, delivery, and ordering information, please contact Maxim/Dallas Direct! at , or visit Maxim s website at

2 Low-Cost, 3MHz, Single/Quad Op Amps with ABSOLUTE MAXIMUM RATINGS Power-Supply Voltage (V CC to V EE )...-.3V to +6V IN_+, IN_-, OUT_,...(V EE -.3V) to (V CC +.3V) Output Short-Circuit Duration to V CC or V EE...Continuous Continuous Power Dissipation (T A = +7 C) 5-Pin SOT3 (derate 8.7mW/ C above +7 C)...696mW 4-Pin SO (derate 8.33mW/ C above +7 C)...667mW 4-Pin TSSOP (derate mw/ C above +7 C)...77mW Operating Temperature Range...-4 C to +85 C Junction Temperature...+5 C Storage Temperature Range C to +5 C Lead Temperature (soldering, s)...+3 C Stresses beyond those listed under Absolute Maximum Ratings may cause permanent damage to the device. These are stress ratings only, and functional operation of the device at these or at any other conditions beyond those indicated in the operational sections of the specifications is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability. DC ELECTRICAL CHARACTERISTICS (V CC = 5V, V EE =, V CM = V CC /, V OUT = V CC /, R L = to V CC /, C BYPASS =.µf, T A = T MIN to T MAX, unless otherwise noted. Typical values are at T A = +5 C.) (Note ) PARAMETER SYMBOL CONDITIONS MIN TYP MAX UNITS Input Common-Mode Voltage Range V CM Guaranteed by CMRR V EE -. T A = +5 C. Input Offset Voltage V OS T A = -4 C to +85 C 8 V CC -.5 V mv Input Offset Voltage Matching MAX4386E mv Input Offset Voltage Tempco TC VOS 8 µv/ C Input Bias Current I B 6.5 µa Input Offset Current I OS.5 7 µa Differential mode (-V V IN +V) 7 kω Input Resistance R IN Common mode (-.V V CM +.75V) 3 MΩ Common-Mode Rejection Ratio CMRR V EE -.V V CM V CC -.5V 7 95 db.5v V OUT 4.75V, R L = kω 5 6.8V V OUT 4.5V, R L = 5Ω Open-Loop Gain A VOL V V OUT 4V, R L = 5Ω 58 db R L = kω V CC - V OH.5.7 V OL - V EE.5.5 Output Voltage Swing V OUT R L = 5Ω V CC - V OH.3.5 V OL - V EE.5.8 R L = 75Ω V CC - V OH.5.8 V OL - V EE.5.75 V R L = 75Ω to V CC - V OH.7 ground V OL - V EE.5.5 Output Current I OUT Sinking from R L = 5Ω to V CC 4 55 Sourcing into R L = 5Ω to V EE 5 5 ma Output Short-Circuit Current I SC Sinking or sourcing ± ma Open-Loop Output Resistance R OUT 8 Ω Power-Supply Rejection Ratio PSRR V S = 4.5V to 5.5V 5 6 db

3 Low-Cost, 3MHz, Single/Quad Op Amps with DC ELECTRICAL CHARACTERISTICS (continued) (V CC = 5V, V EE =, V CM = V CC /, V OUT = V CC /, R L = to V CC /, C BYPASS =.µf, T A = T MIN to T MAX, unless otherwise noted. Typical values are at T A = +5 C.) (Note ) PARAMETER SYMBOL CONDITIONS MIN TYP MAX UNITS Operating Supply Voltage Range Quiescent Supply Current (per Amplifier) ESD Protection Voltage (Note ) AC ELECTRICAL CHARACTERISTICS V S Guaranteed by PSRR V I S ma Human Body Model ±5 IEC -4- Contact Discharge ±8 IEC -4- Air-Gap Discharge ±5 (V CC = 5V, V EE =, V CM =.5V, R L = Ω to V CC /, V OUT = V CC /, A VCL = V/V, T A = +5 C, unless otherwise noted.) PARAMETER SYMBOL CONDITIONS MIN TYP MAX UNITS Small-Signal -3dB Bandwidth BW SS V OUT = mv P-P 3 MHz Large-Signal -3dB Bandwidth BW LS 8 MHz Small-Signal.dB Gain Flatness Large-Signal.dB Gain Flatness BW.dBSS V OUT = mv P-P 33 MHz BW.dBLS 3 MHz Slew Rate SR V OUT = V step 45 V/µs Settling Time to.% t S V OUT = V step 4 ns Rise/Fall Time t R, t F V OUT = mv P-P 4 ns Spurious-Free Dynamic Range SFDR f C = 5MHz, -6 dbc Harmonic Distortion HD nd harmonic -7 f C = 5MHz, 3rd harmonic -6 total harmonic -58 kv dbc Two-Tone, Third-Order Intermodulation Distortion IP3 f = 4.7MHz, f = 4.8MHz, V OUT = V P-P -6 dbc Channel-to-Channel Isolation CH ISO Specified at DC -95 db Input db Compression Point f C = MHz, A VCL = V/V 3 dbm Differential Phase Error DP NTSC, R L = 5Ω. Degrees Differential Gain Error DG NTSC, R L = 5Ω. % Input Noise-Voltage Density e n f = khz.5 nv/ Hz Input Noise-Current Density i n f = khz pa/ Hz Input Capacitance C IN 8 pf Output Impedance Z OUT f = MHz. Ω Note : All devices are % production tested at T A = +5 C. Specifications over temperature limits are guaranteed by design. Note : ESD protection is specified for test point A and test point B only (Figure 6). 3

4 Low-Cost, 3MHz, Single/Quad Op Amps with Typical Operating Characteristics (V CC = 5V, V EE =, V CM =.5V, A VCL = V/V, R L = Ω to V CC /, T A = +5 C, unless otherwise noted.) GAIN (db) GAIN (db) SMALL-SIGNAL GAIN vs. FREQUENCY 4 V OUT = mv P-P k M M M LARGE-SIGNAL GAIN FLATNESS vs. FREQUENCY -.6 k M M M G MAX4385E/86E toc G MAX4385E/86E toc4 GAIN (db) OUTPUT IMPEDANCE (Ω) -6.. k LARGE-SIGNAL GAIN vs. FREQUENCY k M M M OUTPUT IMPEDANCE vs. FREQUENCY M M M G MAX4385E/86E toc G MAX4385E/86E toc5 GAIN (db) DISTORTION (dbc) k SMALL-SIGNAL GAIN FLATNESS vs. FREQUENCY V OUT = mv P-P k M M M DISTORTION vs. FREQUENCY A VCL = V/V 3RD HARMONIC M ND HARMONIC M MAX4385E/86E toc3 G MAX4385E/86E toc6 M DISTORTION (dbc) k DISTORTION vs. FREQUENCY A VCL = V/V 3RD HARMONIC M ND HARMONIC M MAX4385E/86E toc7 M DISTORTION (dbc) k DISTORTION vs. FREQUENCY A VCL = 5V/V 3RD HARMONIC M ND HARMONIC M MAX4385E/86E toc8 M DISTORTION (dbc) DISTORTION vs. RESISTIVE LOAD f O = 5MHz A VCL = V/V ND HARMONIC 3RD HARMONIC R LOAD (Ω) MAX4385E/86E toc9 4

5 Low-Cost, 3MHz, Single/Quad Op Amps with Typical Operating Characteristics (continued) (V CC = 5V, V EE =, V CM =.5V, A VCL = V/V, R L = Ω to V CC /, T A = +5 C, unless otherwise noted.) DISTORTION (dbc) PSR (db) DISTORTION vs. VOLTAGE SWING f O = 5MHz A VCL = V/V 3RD HARMONIC -7 ND HARMONIC VOLTAGE SWING (V P-P ) POWER-SUPPLY REJECTION vs. FREQUENCY MAX4385E/86E toc MAX4385E/86E toc3 DIFF PHASE (DEGREES) DIFF GAIN (PERCENT) OUTPUT VOLTAGE SWING (V) DIFFERENTIAL GAIN AND PHASE IRE IRE OUTPUT VOLTAGE SWING vs. RESISTIVE LOAD V CC - V OH V OL - V EE MAX4385E/86E toc MAX4385E/86E toc4 CMR (db) INPUT 5mV/div OUTPUT 5mV/div COMMON-MODE REJECTION vs. FREQUENCY k M M M SMALL-SIGNAL PULSE RESPONSE A VCL = V/V MAX4385E/86E toc G MAX4385E/86E toc5-7 k M M M G R LOAD (Ω) ns/div SMALL-SIGNAL PULSE RESPONSE SMALL-SIGNAL PULSE RESPONSE LARGE-SIGNAL PULSE RESPONSE INPUT 5mV/div A VCL = V/V R F = Ω MAX4385E/86E toc6 INPUT mv/div A VCL = 5V/V R F = 5Ω MAX4385E/86E toc7 INPUT V/div A VCL = V/V MAX4385E/86E toc8 OUTPUT 5mV/div OUTPUT 5mV/div OUTPUT V/div ns/div ns/div ns/div 5

6 Low-Cost, 3MHz, Single/Quad Op Amps with Typical Operating Characteristics (continued) (V CC = 5V, V EE =, V CM =.5V, A VCL = V/V, R L = Ω to V CC /, T A = +5 C, unless otherwise noted.) INPUT 5mV/div OUTPUT V/div CURRENT NOISE (pa/ Hz) LARGE-SIGNAL PULSE RESPONSE CURRENT NOISE vs. FREQUENCY R L = Ω ns/div A VCL = V/V R F = Ω MAX4385E/86E toc9 MAX4385E/86E toc INPUT mv/div OUTPUT V/div RISO (Ω) LARGE-SIGNAL PULSE RESPONSE ns/div ISOLATION RESISTANCE vs. CAPACITIVE LOAD A VCL = 5V/V R F = 5Ω MAX4385E/86E toc MAX4385E/86E toc3 VOLTAGE NOISE (nv/ Hz) BANDWIDTH (MHz) VOLTAGE NOISE vs. FREQUENCY R L = Ω k k k SMALL-SIGNAL BANDWIDTH vs. LOAD RESISTANCE MAX4385E/86E toc MAX4385E/86E toc4 k k k C LOAD (pf) R LOAD (Ω) OPEN-LOOP GAIN (db) OPEN-LOOP GAIN vs. RESISTIVE LOAD V CC = 5V MAX4385E/86E toc5 CROSSTALK (db) CROSSTALK vs. FREQUENCY MAX4385E/86E toc6 k k R LOAD (Ω) - k M M M G 6

7 Low-Cost, 3MHz, Single/Quad Op Amps with Typical Operating Characteristics (continued) (V CC = 5V, V EE =, V CM =.5V, A VCL = V/V, R L = Ω to V CC /, T A = +5 C, unless otherwise noted.) INPUT OFFSET VOLTAGE (mv) INPUT OFFSET VOLTAGE vs. TEMPERATURE V CC = 5V TEMPERATURE ( C) MAX4385E/86E toc7 INPUT BIAS CURRENT (µa) INPUT BIAS CURRENT vs. TEMPERATURE V CC = 5V TEMPERATURE ( C) MAX4385E/86E toc8 SUPPLY CURRENT (ma) SUPPLY CURRENT vs. TEMPERATURE V CC = 5V TEMPERATURE ( C) MAX4385E/86E toc9 Pin Description PIN MAX4385E MAX4386E NAME FUNCTION SOT3 SO/TSSOP OUT Amplifier Output V EE Negative Power Supply 3 IN+ Noninverting Input 4 IN- Inverting Input 5 4 V CC Positive Power Supply. Connect a.µf and.µf capacitor to GND. OUTA Amplifier A Output INA- Amplifier A Inverting Input 3 INA+ Amplifier A Noninverting Input 5 INB+ Amplifier B Noninverting Input 6 INB- Amplifier B Inverting Input 7 OUTB Amplifier B Output 8 OUTC Amplifier C Output 9 INC- Amplifier C Inverting Input INC+ Amplifier C Noninverting Input IND+ Amplifier D Noninverting Input 3 IND- Amplifier D Inverting Input 4 OUTD Amplifier D Output 7

8 Low-Cost, 3MHz, Single/Quad Op Amps with Detailed Description The are single/quad, 5V, rail-torail, voltage-feedback amplifiers that employ currentfeedback techniques to achieve 45V/µs slew rates and 3MHz bandwidths. High ±5kV ESD protection guards against unexpected discharge. Excellent harmonic distortion and differential gain/phase performance make these amplifiers an ideal choice for a wide variety of video and RF signal-processing applications. Applications Information The output voltage swings to within 5mV of each supply rail. Local feedback around the output stage ensures low open-loop output impedance to reduce gain sensitivity to load variations. The input stage permits common-mode voltages beyond V EE and to within.5v of the positive supply rail. Choosing Resistor Values Unity-Gain Configuration The are internally compensated for unity gain. When configured for unity gain, a 4Ω resistor (RF) in series with the feedback path optimizes AC performance. This resistor improves AC response by reducing the Q of the parallel LC circuit formed by the parasitic feedback capacitance and inductance. Video Line Driver The are low-power, voltagefeedback amplifiers featuring bandwidths up to 3MHz,.dB gain flatness to 3MHz. They are designed to minimize differential-gain error and differential-phase error to.% and., respectively. They have a 4ns settling time to.%, 45V/µs slew rates, and output-current-drive capability of up to 5mA, making them ideal for driving video loads. Inverting and Noninverting Configurations Select the gain-setting feedback (RF) and input (RG) resistor values to fit your application. Large resistor values increase voltage noise and interact with the amplifier s input and PC board capacitance. This can generate undesirable poles and zeros and decrease bandwidth or cause oscillations. For example, a noninverting gain-of-two configuration (RF = RG) using kω resistors, combined with 8pF of amplifier input capacitance and pf of PC board capacitance, causes a pole at 35.4MHz. Since this pole is within the amplifier bandwidth, it jeopardizes stability. Reducing the kω resistors to Ω extends the pole frequency to 353.8MHz, but could limit output swing by adding Ω in parallel with the amplifier s load resistor (Figures a and b). IN R G IN R G V OUT = -(R F / R G ) V IN Layout and Power-Supply Bypassing These amplifiers operate from a single 5V power supply. Bypass VCC to ground with.µf and.µf capacitors as close to the pin as possible. Maxim recommends using microstrip and stripline techniques to obtain full bandwidth. To ensure that the PC board does not degrade the amplifier s performance, design it for a frequency greater than GHz. Pay careful attention to inputs and outputs to avoid large parasitic capacitance. Regardless of whether you use a constant-impedance board, observe the following design guidelines: Do not use wire-wrap boards; they are too inductive. Do not use IC sockets; they increase parasitic capacitance and inductance. Use surface mount instead of through-hole components for better high-frequency performance. Use a PC board with at least two layers; it should be as free from voids as possible. Keep signal lines as short and as straight as possible. Do not make 9 turns; round all corners. R F MAX438_E Figure b. Inverting Gain Configuration R F MAX438_E V OUT = [+ (R F / R G )] V IN Figure a. Noninverting Gain Configuration V OUT V OUT 8

9 Low-Cost, 3MHz, Single/Quad Op Amps with R G V IN R F MAX438_E R ISO Figure. Driving a Capacitive Load Through an Isolation Resistor Rail-to-Rail Outputs, Ground-Sensing Inputs The input common-mode range extends from (VEE - mv) to (VCC -.5V) with excellent common-mode rejection. Beyond this range, the amplifier output is a nonlinear function of the input, but does not undergo phase reversal or latchup. The output swings to within 5mV of either power-supply rail with a kω load. The input ground sensing and the rail-to-rail output substantially increase the dynamic range. The input can swing.95vp-p and the output can swing 4.9VP-P with minimal distortion. Output Capacitive Loading and Stability The are optimized for AC performance and do not drive highly reactive loads, which decreases phase margin and may produce excessive ringing and oscillation. Figure shows a circuit that eliminates this problem. Figure 3 is a graph of the Optimal Isolation Resistor (RS) vs. Capacitive Load. Figure 4 shows how a capacitive load causes excessive peaking of the amplifier s frequency response if the capacitor is not isolated from the amplifier by a resistor. A small isolation resistor (usually Ω to 5Ω) placed before the reactive load prevents ringing and oscillation. At higher capacitive loads, the interaction of the load capacitance and the isolation resistor controls the AC performance. Figure 5 shows the effect of a 5Ω isolation resistor on closed-loop response. C L V OUT RISO (Ω) GAIN (db) ISOLATION RESISTANCE vs. CAPACITIVE LOAD C LOAD (pf) Figure 3. Isolation Resistance vs. Capacitive Load C L = pf C L = 5pF k M M M C L = 5pF Figure 4. Small-Signal Gain vs. Frequency with Load Capacitance and No Isolation Resistor GAIN (db) R ISO = 5Ω C L = 68pF C L = pf k M M M C L = 47pF G G Figure 5. Small-Signal Gain vs. Frequency with Load Capacitance and 7Ω Isolation Resistor 9

10 Low-Cost, 3MHz, Single/Quad Op Amps with ESD Protection As with all Maxim devices, ESD protection structures are incorporated on all pins to protect against ESD encountered during handling and assembly. Input and output pins of the have extra protection against static electricity. Maxim s engineers have developed state-of-the-art structures enabling these pins to withstand ESD up to ±5kV without damage when placed in the test circuit (Figure 6). The are characterized for protection to the following limits: ±5kV using the Human Body Model ±8kV using the Contact Discharge method specified in IEC -4- ±5kV using the Air-Gap Discharge method specified in IEC -4- Human Body Model Figure 7 shows the Human Body Model, and Figure 8 shows the current waveform it generates when discharged into a low impedance. This model consists of a 5pF capacitor charged to the ESD voltage of interest, and then discharged into the test device through a.5kω resistor. TEST POINT A IEC -4- The IEC -4- standard covers ESD testing and performance of finished equipment; it does not specifically refer to ICs. The enable the design of equipment that meets the highest level (Level 4) of IEC -4- without the need for additional ESD protection components. The major difference between tests done using the Human Body Model and IEC - 4- is higher peak current in IEC -4-. Because series resistance is lower in the IEC -4- model, the ESD-withstand voltage measured to this standard is generally lower than that measured using the Human Body. Figure shows the IEC -4- model and Figure 9 shows the current waveform for the ±8kV IEC -4- Level 4 ESD Contact Discharge test. The Air- Gap test involves approaching the device with a charged probe. The Contact Discharge method connects the probe to the device before the probe is energized. HIGH- VOLTAGE DC SOURCE R C = MΩ CHARGE CURRENT LIMIT RESISTOR C S = 5pF R D =.5kΩ DISCHARGE RESISTANCE STORAGE CAPACITOR Figure 7. Human Body ESD Model AMPERES 75Ω I P % 9% 36.8% Ω Figure 6. ESD Test Circuit 5V MAX438_E Ω V EE Ir C BYPASS.µF 75Ω TEST POINT B DEVICE UNDER TEST PEAK-TO-PEAK RINGING (NOT DRAWN TO SCALE) % t RL TIME t DL CURRENT WAVEFORM Figure 8. Human Body Current Waveform

11 Low-Cost, 3MHz, Single/Quad Op Amps with HIGH- VOLTAGE DC SOURCE R C 5MΩ TO MΩ CHARGE CURRENT LIMIT RESISTOR C S 5pF R D 33Ω DISCHARGE RESISTANCE STORAGE CAPACITOR Figure 9. IEC -4- ESD Test Model DEVICE UNDER TEST Pin Configurations (continued) IPEAK % 9% % tr =.7ns TO ns I 3ns Figure. IEC -4- ESD Generator Current Waveform 6ns Chip Information MAX4385E TRANSISTOR COUNT: 4 MAX4386E TRANSISTOR COUNT: 64 t TOP VIEW OUTA 4 OUTD IND- INA- 3 INA+ 3 IND+ V CC 4 MAX4386E V EE INB+ 5 INC+ INC- INB- 6 9 OUTB 7 8 OUTC TSSOP/SO

12 Low-Cost, 3MHz, Single/Quad Op Amps with Package Information (The package drawing(s) in this data sheet may not reflect the most current specifications. For the latest package outline information, go to SOT-3 5L.EPS PACKAGE OUTLINE, SOT-3, 5L -57 E TSSOP4.4mm.EPS PACKAGE OUTLINE, TSSOP 4.4mm BODY -66 G

13 Low-Cost, 3MHz, Single/Quad Op Amps with Package Information (continued) (The package drawing(s) in this data sheet may not reflect the most current specifications. For the latest package outline information, go to N TOP VIEW D E H INCHES MILLIMETERS DIM A A MIN.53.4 MAX.69. MIN.35. MAX.75.5 B C e.5 BSC.7 BSC E H L VARIATIONS: DIM D D D INCHES MILLIMETERS MIN MAX MIN MAX N MS AA AB AC SOICN.EPS A C e B A FRONT VIEW L SIDE VIEW -8 PROPRIETARY INFORMATION TITLE: PACKAGE OUTLINE,.5" SOIC APPROVAL DOCUMENT CONTROL NO. REV. -4 B Maxim cannot assume responsibility for use of any circuitry other than circuitry entirely embodied in a Maxim product. No circuit patent licenses are implied. Maxim reserves the right to change the circuitry and specifications without notice at any time. Maxim Integrated Products, San Gabriel Drive, Sunnyvale, CA Maxim Integrated Products Printed USA is a registered trademark of Maxim Integrated Products, Inc.