JFET Input Instrumentation Amplifier with Rail-to-Rail Output in MSOP Package AD8 FEATURES Low input currents pa maximum input bias current (B grade).6 pa maximum input offset current (B grade) High CMRR db CMRR (minimum), G = (B grade) 8 db CMRR (minimum) to 5 khz, G = (B grade) Excellent ac specifications and low power.5 MHz bandwidth (G = ) 4 nv/ Hz input noise ( khz) Slew rate: V/μs 75 μa quiescent supply current (maximum) Versatile MSOP package Rail-to-rail output Input voltage range to below negative supply rail 4 kv ESD protection 4.5 V to 36 V single supply ±.5 V to ±8 V dual supply Gain set with single resistor (G = to ) Qualified for automotive applications APPLICATIONS Medical instrumentation Precision data acquisition Transducer interfaces GENERAL DESCRIPTION The AD8 is the first single-supply, JFET input instrumentation amplifier available in an MSOP package. Designed to meet the needs of high performance, portable instrumentation, the AD8 has a minimum common-mode rejection ratio (CMRR) of 86 db at dc and a minimum CMRR of 8 db at 5 khz for G =. Maximum input bias current is pa and typically remains below 3 pa over the entire industrial temperature range. Despite the JFET inputs, the AD8 typically has a noise corner of only Hz. With the proliferation of mixed-signal processing, the number of power supplies required in each system has grown. The AD8 is designed to alleviate this problem. The AD8 can operate on a ±8 V dual supply, as well as on a single +5 V supply. Its rail-to-rail output stage maximizes dynamic range on the low voltage supplies common in portable applications. Its ability to run on a single 5 V supply eliminates the need to use higher voltage, dual supplies. The AD8 draws a maximum of 75 μa of quiescent current, making it ideal for battery powered devices. INPUT BIAS CURRENT (A) n n p p p.p PIN CONFIGURATION IN R G R G 3 +IN 4 AD8 TOP VIEW (Not to Scale) Figure. 8 7 6 5 I BIAS +V S V OUT REF 5 5 5 5 75 5 5 TEMPERATURE ( C) Figure. Input Bias Current and Offset Current vs. Temperature Gain is set from to with a single resistor. Increasing the gain increases the common-mode rejection. Measurements that need higher CMRR when reading small signals benefit when the AD8 is set for large gains. A reference pin allows the user to offset the output voltage. This feature is useful when interfacing with analog-to-digital converters. The AD8 is available in an MSOP that takes roughly half the board area of an SOIC. Performance for the A and B grade is specified over the industrial temperature range of 4 C to +85 C, and the W grade is specified over the automotive temperature range of 4 C to +5 C. I OS 3579-5 3579-59 Rev. B Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. Specifications subject to change without notice. No license is granted by implication or otherwise under any patent or patent rights of Analog Devices. Trademarks and registered trademarks are the property of their respective owners. One Technology Way, P.O. Box 96, Norwood, MA 6-96, U.S.A. Tel: 78.39.47 www.analog.com Fax: 78.46.33 6 Analog Devices, Inc. All rights reserved.
* PRODUCT PAGE QUICK LINKS Last Content Update: 8//7 COMPARABLE PARTS View a parametric search of comparable parts. EVALUATION KITS AD6x, AD8x, AD84x Series InAmp Evaluation Board DOCUMENTATION Application Notes AN-4: Instrumentation Amplifier Common-Mode Range: The Diamond Plot Data Sheet AD8-DSCC: Military Data Sheet AD8-EP: Enhanced Product Data Sheet AD8: JFET Input Instrumentation Amplifier with Railto-Rail Output in MSOP Package Data Sheet Technical Books A Designer's Guide to Instrumentation Amplifiers, 3rd Edition, 6 User Guides UG-8: PLC Demo System, Industrial Process Control Demo System TOOLS AND SIMULATIONS AD8 SPICE Macro Model REFERENCE DESIGNS CN67 CN4 REFERENCE MATERIALS Technical Articles Auto-Zero Amplifiers Biopotential Electrode Sensors in ECG/EEG/EMG Systems High-performance Adder Uses Instrumentation Amplifiers MS-6: Mitigation Strategies for ECG Design Challenges Part : Simplifying Design of Industrial Process-Control Systems with PLC Evaluation Boards Part : Simplifying Design of Industrial Process-Control Systems with PLC Evaluation Boards DESIGN RESOURCES AD8 Material Declaration PCN-PDN Information Quality And Reliability Symbols and Footprints DISCUSSIONS View all AD8 EngineerZone Discussions. SAMPLE AND BUY Visit the product page to see pricing options. TECHNICAL SUPPORT Submit a technical question or find your regional support number. DOCUMENT FEEDBACK Submit feedback for this data sheet. This page is dynamically generated by Analog Devices, Inc., and inserted into this data sheet. A dynamic change to the content on this page will not trigger a change to either the revision number or the content of the product data sheet. This dynamic page may be frequently modified.
TABLE OF CONTENTS Features... Applications... Pin Configuration... General Description... Revision History... Specifications... 3 Absolute Maximum Ratings... 8 ESD Caution... 8 Pin Configuration and Function Descriptions... 9 Typical Performance Characteristics... Theory of Operation... 9 Gain Selection... Layout... Reference Terminal... Power Supply Regulation and Bypassing... Input Bias Current Return Path... Input Protection... RF Interference... Common-Mode Input Voltage Range... Driving an ADC... Applications Information... 3 AC-Coupled Instrumentation Amplifier... 3 Differential Output... 3 Electrocardiogram Signal Conditioning... 5 Outline Dimensions... 6 Ordering Guide... 6 Automotive Products... 6 REVISION HISTORY 5/ Rev. A to Rev. B Added W Grade... Universal Changes to Features Section and General Description Section. Changes to Specifications Section and Table... 3 Changes to Table... 5 Updated Outline Dimensions... 6 Changes to Ordering Guide... 6 Added Automotive Products Section... 6 5/7 Rev. to Rev. A Changes to Table... 3 Changes to Table... 5 Changes to Table 3... 8 Changes to Figure 6 and Figure 7... Changes to Figure 3 and Figure 4... 3 Changes to Theory of Operation... 9 Changes to Layout... Changes to Ordering Guide... 6 4/6 Revision : Initial Version Rev. B Page of 8
SPECIFICATIONS VS+ = 5 V, VS = 5 V, VREF = V, TA = 5 C, TOPR = 4 C to +85 C for A and B grades. TOPR = 4 C to +5 C for W grade, G =, RL = kω, unless otherwise noted. AD8 Table. A Grade B Grade W Grade Parameter Test Conditions Min Typ Max Min Typ Max Min Typ Max Unit COMMON-MODE REJECTION RATIO (CMRR) TA for A, B grades, TOPR for W grade CMRR DC to 6 Hz with VCM = ± V kω Source Imbalance G = 78 86 77 db G = 94 9 db G = 94 9 db G = 94 9 db CMRR at 5 khz VCM = ± V G = 74 8 7 db G = 84 9 8 db G = 84 9 8 db G = 84 9 8 db NOISE RTI noise = (eni + (eno/g) ), TA Voltage Noise, khz Input Voltage Noise, eni VIN+, VIN = V 4 4 7 4 nv/ Hz Output Voltage Noise, eno VIN+, VIN = V 9 9 9 nv/ Hz RTI,. Hz to Hz G = 5 5 5 μv p-p G =.8.8.8 μv p-p Current Noise f = khz fa/ Hz VOLTAGE OFFSET VOS = VOSI + VOSO/G Input Offset, VOSI TA 5 +5 5 +5 5 +5 μv Average TC TOPR + 5 +5 + μv/ C Output Offset, VOSO TA 75 +75 5 +5 75 +75 μv Average TC TOPR + 5 +5 + μv/ C Offset RTI vs. Supply (PSR) VS = ±5 V to ±5 V, TA for A, B grades, TOPR for W grade G = 86 86 8 db G = 96 9 db G = 96 9 db G = 96 9 db INPUT CURRENT Input Bias Current TA 5 5 pa Over Temperature TOPR.3.3 na Input Offset Current TA.6 pa Over Temperature TOPR.5.5 na DYNAMIC RESPONSE Small Signal Bandwidth, 3 db TA G = 5 5 5 khz G = 8 8 8 khz G = khz G = 4 4 4 khz Rev. B Page 3 of 8
A Grade B Grade W Grade Parameter Test Conditions Min Typ Max Min Typ Max Min Typ Max Unit Settling Time.% V step, TA G = 5 5 5 μs G = 4.3 4.3 4.3 μs G = 8. 8. 8. μs G = 58 58 58 μs Settling Time.% V step, TA G = 6 6 6 μs G = 4.6 4.6 4.6 μs G = 9.6 9.6 9.6 μs G = 74 74 74 μs Slew Rate G = to TA V/μs GAIN G = + (49.4 kω/rg), TA for A, B grades, TOPR for W grade Gain Range V/V Gain Error VOUT = ± V G =.6 +.6.4 +.4. +. % G =.3 +.3. +..8 +.8 % G =.3 +.3. +..8 +.8 % G =.3 +.3. +..8 +.8 % Gain Nonlinearity VOUT = V to + V, TA G = RL = kω 5 5 5 ppm G = RL = kω 5 5 5 ppm G = RL = kω 3 6 3 6 3 6 ppm G = RL = kω 4 5 4 5 4 5 ppm G = RL = kω 5 5 5 ppm G = RL = kω 5 5 5 ppm G = RL = kω 5 75 5 75 5 75 ppm Gain vs. Temperature G = 3 5 3 ppm/ C G > 5 5 5 ppm/ C INPUT Impedance (Pin to TA 4 5 4 5 4 5 GΩ pf Ground) Input Operating Voltage Range 3 VS = ±.5 V to ±8 V for dual supplies VS. +VS VS. +VS VS. +VS V Over Temperature TOPR VS. OUTPUT Output Swing RL = kω, TA 4.7 +4.7 4.7 +4.7 4.7 +4.7 V Over Temperature TOPR 4.6 +4.6 4.6 +4.6 4.3 +4.3 V Short-Circuit Current TA 5 5 5 ma REFERENCE INPUT TA kω RIN 4 4 4 μa IIN VIN+, VIN = V 7 7 7 V Voltage Range VS +VS VS +VS +VS V/V Gain to Output TA ±. +VS. VS. ±. +VS. VS. +VS. ±. V V/V Rev. B Page 4 of 8
A Grade B Grade W Grade Parameter Test Conditions Min Typ Max Min Typ Max Min Typ Max Unit POWER SUPPLY V Operating Range ±.5 4 ±8 ±.5 4 ±8 ±.5 4 ±8 μa Quiescent Current TA 75 75 75 μa Over Temperature TOPR 85 85 μa TEMPERATURE RANGE For Specified Performance TOPR 4 +85 4 +85 4 +5 C When the output sinks more than 4 ma, use a 47 pf capacitor in parallel with the load to prevent ringing. Otherwise, use a larger load, such as kω. Differential and common-mode input impedance can be calculated from the pin impedance: ZDIFF = (ZPIN); ZCM = ZPIN/. 3 The AD8 can operate up to a diode drop below the negative supply but the bias current increases sharply. The input voltage range reflects the maximum allowable voltage where the input bias current is within the specification. 4 At this supply voltage, ensure that the input common-mode voltage is within the input voltage range specification. VS + = 5 V, VS = V, VREF =.5 V, TA = 5 C, TOPR = 4 C to +85 C for A and B grades. TOPR = 4 C to +5 C for W grade, G =, RL = kω, unless otherwise noted. Table. A Grade B Grade W Grade Parameter Test Conditions Min Typ Max Min Typ Max Min Typ Max Unit COMMON-MODE REJECTION RATIO (CMRR) TA for A, B grades, TOPR for W grade CMRR DC to 6 Hz with VCM = to.5 V kω Source Imbalance G = 78 86 77 db G = 94 9 db G = 94 9 db G = 94 9 db CMRR at 5 khz VCM = to.5 V G = 74 8 7 db G = 84 9 8 db G = 84 9 8 db G = 84 9 8 db NOISE RTI noise = (eni + (eno/g) ), TA Voltage Noise, khz VS = ±.5 V Input Voltage Noise, eni VIN+, VIN = V, VREF = 4 4 7 4 nv/ Hz V Output Voltage Noise, eno VIN+, VIN = V, VREF = 9 9 9 nv/ Hz V RTI,. Hz to Hz G = 5 5 5 μv p-p G =.8.8.8 μv p-p Current Noise f = khz fa/ Hz VOLTAGE OFFSET VOS = VOSI + VOSO/G Input Offset, VOSI TA 3 +3 + 3 +3 μv Average TC TOPR + 5 +5 μv/ C Output Offset, VOSO TA 8 +8 6 +6 8 +8 μv Average TC TOPR + 5 +5 + μv/ C Offset RTI vs. Supply (PSR) TA for A, B grades, TOPR for W grade G = 86 86 8 db G = 96 9 db G = 96 9 db G = 96 9 db Rev. B Page 5 of 8
A Grade B Grade W Grade Parameter Test Conditions Min Typ Max Min Typ Max Min Typ Max Unit INPUT CURRENT Input Bias Current TA 5 5 pa Over Temperature TOPR.3.3 na Input Offset Current TA.6 pa Over Temperature TOPR.5.5 na DYNAMIC RESPONSE TA Small Signal Bandwidth, 3 db G = 5 5 5 khz G = 8 8 8 khz G = khz G = 4 4 4 khz Settling Time.% TA G = 3 V step.5.5.5 μs G = 4 V step.5.5.5 μs G = 4 V step 7.5 7.5 7.5 μs G = 4 V step 3 3 3 μs Settling Time.% TA G = 3 V step 3.5 3.5 3.5 μs G = 4 V step 3.5 3.5 3.5 μs G = 4 V step 8.5 8.5 8.5 μs G = 4 V step 37 37 37 μs Slew Rate G = to TA V/μs GAIN G = + (49.4 kω/rg), TA for A, B grades, TOPR for W grade Gain Range V/V Gain Error VOUT =.3 V to.9 V for G =, VOUT =.3 V to 3.8 V for G > G =.6 +.6.4 +.4. +. % G =.3 +.3. +..8 +.8 % G =.3 +.3. +..8 +.8 % G =.3 +.3. +..8 +.8 % Nonlinearity VOUT =.3 V to.9 V for G =, VOUT =.3 V to 3.8 V for G >, TA G = RL = kω 35 5 35 5 5 ppm G = RL = kω 35 5 35 5 5 ppm G = RL = kω 5 75 5 75 75 ppm G = RL = kω 65 75 65 75 75 ppm G = RL = kω 35 5 35 5 5 ppm G = RL = kω 35 5 35 5 5 ppm G = RL = kω 5 75 5 75 75 ppm Gain vs. Temperature G = 3 5 3 ppm/ C G > 5 5 5 ppm/ C INPUT Impedance (Pin to TA 4 6 4 6 4 6 GΩ pf Ground) Input Voltage Range 3 TA. +VS. +VS V Over Temperature TOPR. +VS.. +VS.. +VS. V Rev. B Page 6 of 8
A Grade B Grade W Grade Parameter Test Conditions Min Typ Max Min Typ Max Min Typ Max Unit OUTPUT Output Swing RL = kω.5 4.85.5 4.85.5 4.85 V Over Temperature TOPR. 4.8. 4.8.3 4.7 V Short-Circuit Current 5 5 5 ma REFERENCE INPUT TA RIN 4 4 4 kω IIN VIN+, VIN = V 7 7 7 μa Voltage Range VS +VS VS +VS VS +VS V Gain to Output TA ±. ±. ±. POWER SUPPLY Operating Range 4.5 36 4.5 36 4.5 36 V Quiescent Current TA 75 75 75 μa Over Temperature TOPR 85 85 μa TEMPERATURE RANGE TOPR, For Specified Performance TOPR 4 +85 4 +85 4 +5 C When the output sinks more than 4 ma, use a 47 pf capacitor in parallel with the load to prevent ringing. Otherwise, use a larger load, such as kω. Differential and common-mode impedance can be calculated from the pin impedance: ZDIFF = (ZPIN); ZCM = ZPIN/. 3 The AD8 can operate up to a diode drop below the negative supply but the bias current increases sharply. The input voltage range reflects the maximum allowable voltage where the input bias current is within the specification. V/V Rev. B Page 7 of 8
ABSOLUTE MAXIMUM RATINGS Table 3. Parameter Rating Supply Voltage ±8 V Power Dissipation See Figure 3 Output Short-Circuit Current Indefinite Input Voltage (Common Mode) ±Vs Differential Input Voltage ±Vs Storage Temperature Range 65 C to +5 C Operating Temperature Range 4 C to +5 C Lead Temperature (Soldering sec) 3 C Junction Temperature 4 C θja (4-Layer JEDEC Standard Board) 35 C/W Package Glass Transition Temperature 4 C ESD (Human Body Model) 4 kv ESD (Charge Device Model) kv ESD (Machine Model).4 kv Assumes the load is referenced to midsupply. Temperature for specified performance is 4 C to +85 C. For performance to 5 C, see the Typical Performance Characteristics section. Stresses above those listed under Absolute Maximum Ratings may cause permanent damage to the device. This is a stress rating only; functional operation of the device at these or any other conditions above those indicated in the operational section of this specification is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability. Figure 3 shows the maximum safe power dissipation in the package vs. the ambient temperature for the MSOP on a 4-layer JEDEC standard board. θja values are approximations. MAXIMUM POWER DISSIPATION (W)..75.5.5..75.5.5 4 4 6 8 AMBIENT TEMPERATURE ( C) Figure 3. Maximum Power Dissipation vs. Ambient Temperature 3579-45 ESD CAUTION Rev. B Page 8 of 8
PIN CONFIGURATION AND FUNCTION DESCRIPTIONS IN AD8 8 +V S R G 7 V OUT R G 3 6 REF +IN 4 5 TOP VIEW (Not to Scale) Figure 4. Pin Configuration 3579-5 Table 4. Pin Function Descriptions Pin No. Mnemonic Description IN Negative Input Terminal (True Differential Input), 3 RG Gain Setting Terminals (Place Resistor Across the RG Pins) 4 +IN Positive Input Terminal (True Differential Input) 5 VS Negative Power Supply Terminal 6 REF Reference Voltage Terminal (Drive This Terminal with a Low Impedance Voltage Source to Level-Shift the Output) 7 VOUT Output Terminal 8 +VS Positive Power Supply Terminal Rev. B Page 9 of 8
TYPICAL PERFORMANCE CHARACTERISTICS 6 4 NUMBER OF UNITS 8 6 4 NUMBER OF UNITS 8 6 4 4 4 CMRR (µv/v) 3579-6 3 4 5 I BIAS (pa) 3579-63 Figure 5. Typical Distribution of CMRR (G = ) Figure 8. Typical Distribution of Input Bias Current NUMBER OF UNITS 8 6 4 NUMBER OF UNITS 8 6 4 V OSI (µv) Figure 6. Typical Distribution of Input Offset Voltage 3579-6.... I OS (pa) Figure 9. Typical Distribution of Input Offset Current 3579-64 NUMBER OF UNITS 8 6 4 VOLTAGE NOISE RTI (nv/ Hz) GAIN = BANDWIDTH ROLL-OFF GAIN = GAIN = GAIN = /GAIN = GAIN = BANDWIDTH ROLL-OFF 5 5 V OSO (µv) Figure 7. Typical Distribution of Output Offset Voltage 3579-6 k k k FREQUENCY (Hz) Figure. Voltage Spectral Density vs. Frequency 3579-4 Rev. B Page of 8
5 3 GAIN = GAIN = BANDWIDTH LIMITED X (X) PSRR (db) 9 7 GAIN = GAIN = 5 5µV/DIV X (X) Figure.. Hz to Hz RTI Voltage Noise (G = ) s/div 3579-4 3 k k k M FREQUENCY (Hz) Figure 4. Positive PSRR vs. Frequency, RTI 3579-35 5 3 GAIN = X (X) PSRR (db) 9 7 GAIN = GAIN = 5 GAIN = µv/div s/div 3579-5 3 k k k M 3579-4 X (X) Figure.. Hz to Hz RTI Voltage Noise (G = ) FREQUENCY (Hz) Figure 5. Negative PSRR vs. Frequency, RTI Δ V OSI (µv) 8 7 6 5 4 3. k TIME (s) Figure 3. Change in Input Offset Voltage vs. Warmup Time 3579-9 INPUT BIAS CURRENT (pa) 9 7 5 3 INPUT OFFSET CURRENT ±5 5.V 5.V INPUT OFFSET CURRENT ±5 INPUT BIAS CURRENT ±5.5 6 8 4 4 8 6 COMMON-MODE VOLTAGE (V) INPUT BIAS CURRENT ±5 Figure 6. Input Bias Current and Input Offset Current vs. Common-Mode Voltage.3.....3.4 INPUT OFFSET CURRENT (pa) 3579-5 Rev. B Page of 8
6 INPUT BIAS CURRENT (A) n n p p p I BIAS I OS CMRR (db) 4 8 GAIN = GAIN = GAIN = GAIN = BANDWIDTH LIMITED.p 5 5 5 5 75 5 5 TEMPERATURE ( C) Figure 7. Input Bias Current and Offset Current vs. Temperature, VS = ±5 V, VREF = V 3579-59 6 4 k k k FREQUENCY (Hz) Figure. CMRR vs. Frequency, kω Source Imbalance 3579-5 n 8 6 CURRENT (A) n p p p I BIAS I OS Δ CMRR (μv/v) 4 4.p 5 5 5 5 75 5 5 TEMPERATURE ( C) Figure 8. Input Bias Current and Offset Current vs. Temperature, VS = +5 V, VREF =.5 V 3579-65 6 8 5 3 3 5 7 9 3 TEMPERATURE ( C) Figure. Change in CMRR vs. Temperature, G = 3579-34 6 7 4 GAIN = 6 5 GAIN = GAIN = 4 3 GAIN = CMRR (db) 8 GAIN = GAIN = BANDWIDTH LIMITED GAIN (db) GAIN = GAIN = 6 4 k k k FREQUENCY (Hz) Figure 9. CMRR vs. Frequency 3579-3 3 4 k k k M M FREQUENCY (Hz) Figure. Gain vs. Frequency 3579- Rev. B Page of 8
X NONLINEARITY (5ppm/DIV) R LOAD = kω R LOAD = kω X NONLINEARITY (5ppm/DIV) R LOAD =kω R LOAD =kω V S = ±5V 8 6 4 4 6 8 3579-6 V S = ±5V 8 6 4 4 6 8 3579-9 OUTPUT VOLTAGE (V) Figure 3. Gain Nonlinearity, G = OUTPUT VOLTAGE (V) Figure 6. Gain Nonlinearity, G = 8 X NONLINEARITY (5ppm/DIV) V S = ±5V R LOAD = kω 8 6 4 4 6 8 OUTPUT VOLTAGE (V) R LOAD = kω Figure 4. Gain Nonlinearity, G = 3579-7 INPUT COMMON-MODE VOLTAGE (V) 6 6 ±5V SUPPLIES 4.8V, +5.5V 4.8V, +.6V 4.8V, 3.3V 4.8V, 8.3V +3V +3V ±5V SUPPLIES 5.3V 5.3V 8 6 8 4 4 8 6 OUTPUT VOLTAGE (V) +4.9V, +5.5V +4.95V, +.6V +4.95V, 3.3V +4.9V, 8.3V Figure 7. Input Common-Mode Voltage Range vs. Output Voltage, G =, VREF = V 3579-37 4 X NONLINEARITY (5ppm/DIV) V S = ±5V R LOAD = kω 8 6 4 4 6 8 OUTPUT VOLTAGE (V) R LOAD =kω Figure 5. Gain Nonlinearity, G = 3579-8 INPUT COMMON-MODE VOLTAGE (V) 3 +.V, +.7V +.V, +.5V +3V +5VSINGLESUPPLY, V REF = +.5V.3V 3 4 5 6 OUTPUT VOLTAGE (V) +4.9V, +.7V +4.9V, +.5V Figure 8. Input Common-Mode Voltage Range vs. Output Voltage, G =, VS = +5 V, VREF =.5 V 3579-36 Rev. B Page 3 of 8
INPUT COMMON-MODE VOLTAGE (V) INPUT COMMON-MODE VOLTAGE (V) 8 6 6 ±5V SUPPLIES 4.9V, +5.4V 4.9V, +.4V 4.9V, 4.V 4.8V, 9V +3V 5.3V +3V ±5V SUPPLIES 5.3V 8 6 8 4 4 8 6 OUTPUT VOLTAGE (V) +4.9V, +5.4V +4.9V, +.5V +4.9V, 4.V +4.9V, 9V Figure 9. Input Common-Mode Voltage Range vs. Output Voltage, G =, VREF = V 4 3 +.V, +.7V +.V,.5V +3V +5V SINGLE SUPPLY, V REF = +.5V.3V 3 4 5 6 OUTPUT VOLTAGE (V) +4.9V, +.7V +4.9V,.5V Figure 3. Input Common-Mode Voltage Range vs. Output Voltage, G =, VS = +5 V, VREF =.5 V V S + 3579-39 3579-38 OUTPUT VOLTAGE SWING (V) REFERRED TO SUPPLY VOLTAGE V S + 3 4 +4 +3 + + +5 C 4 C +5 C +85 C +5 C +85 C +5 C 4 C V S 4 6 8 4 6 8 DUAL SUPPLY VOLTAGE (±V) Figure 3. Output Voltage Swing vs. Supply Voltage, RLOAD = kω, G =, VREF = V OUTPUT VOLTAGE SWING (V) REFERRED TO SUPPLY VOLTAGE V S +..4 +.4 +. V S 4 6 8 4 6 8 DUAL SUPPLY VOLTAGE (±V) Figure 33. Output Voltage Swing vs. Supply Voltage, RLOAD = kω, G =, VREF = V 5 +5 C +85 C +5 C 4 C +5 C +85 C +5 C 4 C 3579-53 3579-54 INPUT VOLTAGE LIMIT (V) + V S 4 C +5 C +5 C +85 C NOTES. THE AD8 CAN OPERATE UP TO A V BE BELOW THE NEGATIVE SUPPLY, BUT THE BIAS CURRENT WILL INCREASE SHARPLY. 4 C +5 C +85 C +5 C 4 6 8 4 6 8 SUPPLY VOLTAGE (V) Figure 3. Input Voltage Limit vs. Supply Voltage, G =, VREF = V 3579-5 OUTPUT VOLTAGE SWING (V) 5 5 +5 C 4 C +5 C +5 C +85 C +85 C +5 C 4 C 5 k k R LOAD (Ω) Figure 34. Output Voltage Swing vs. Load Resistance VS = ±5 V, VREF = V 3579-55 Rev. B Page 4 of 8
OUTPUT VOLTAGE SWING (V) 5 4 C +85 C 4 +5 C +5 C 3 +5 C +5 C +85 C 4 C k k R LOAD (Ω) Figure 35. Output Voltage Swing vs. Load Resistance VS = +5 V, VREF =.5 V 3579-56 X (X) NO LOAD mv/div 47pF 5µs/DIV pf X (X) Figure 38. Small Signal Pulse Response for Various Capacitive Loads, VS = ±5 V, VREF = V 3579-8 V S + OUTPUT VOLTAGE SWING (V) REFERRED TO SUPPLY VOLTAGES 3 4 +4 +3 + +5 C 4 C +85 C +5 C +5 C +85 C +5 C X (X) NO LOAD 47pF pf + 4 C V S 4 6 8 4 6 I OUT (ma) Figure 36. Output Voltage Swing vs. Output Current, VS = ±5 V, VREF = V OUTPUT VOLTAGE SWING (V) REFERRED TO SUPPLY VOLTAGES V S + + + +5 C +5 C +85 C +85 C +5 C +5 C 4 C V S 4 6 8 4 6 I OUT (ma) Figure 37. Output Voltage Swing vs. Output Current, VS = 5 V, VREF =.5 V 3579-57 3579-58 mv/div 5µs/DIV X (X) Figure 39. Small Signal Pulse Response for Various Capacitive Loads, VS = 5 V, VREF =.5 V OUTPUT VOLTAGE SWING (V p-p) 35 3 5 5 5 GAIN =,, GAIN = k k k M M FREQUENCY (Hz) Figure 4. Output Voltage Swing vs. Large Signal Frequency Response 3579-9 3579- Rev. B Page 5 of 8
5V/DIV 5V/DIV X (X).%/DIV 5µs TO.% 6µs TO.% µs/div X (X) Figure 4. Large Signal Pulse Response and Settle Time, G =, RLOAD = kω, VS = ±5 V, VREF = V 3579-46 3579-49 5V/DIV X (X).%/DIV 4.3μs TO.% 4.6μs TO.% X (X) µs/div Figure 4. Large Signal Pulse Response and Settle Time, G =, RLOAD = kω, VS = ±5 V, VREF = V 3579-47 X (X) X (X).%/DIV 58μs TO.% 74μs TO.% X (X) µs/div Figure 44. Large Signal Pulse Response and Settle Time, G =, RLOAD = kω, VS = ±5 V, VREF = V 3579-6 X mv/div X 4µs/DIV Figure 45. Small Signal Pulse Response, G =, RLOAD = kω, CLOAD = pf, VS = ±5 V, VREF = V 5V/DIV X.%/DIV 8.μs TO.% 9.6μs TO.% mv/div X (X) µs/div Figure 43. Large Signal Pulse Response and Settle Time, G =, RLOAD = kω, VS = ±5 V, VREF = V 3579-48 X 4µs/DIV Figure 46. Small Signal Pulse Response, G =, RLOAD = kω, CLOAD = pf, VS = ±5 V, VREF = V 3579-4 Rev. B Page 6 of 8
X mv/div X 4µs/DIV Figure 47 Small Signal Pulse Response, G =, RLOAD = kω, CLOAD = pf, VS = ±5 V, VREF = V 3579- X 3579-5 mv/div X 4µs/DIV Figure 48. Small Signal Pulse Response, G =, RLOAD = kω, CLOAD = pf, VS = ±5 V, VREF = V X X mv/div X 4µs/DIV Figure 5. Small Signal Pulse Response, G =, RLOAD = kω, CLOAD = pf, VS = 5 V, VREF =.5 V X mv/div 3579- X 4µs/DIV Figure 5. Small Signal Pulse Response, G =, RLOAD = kω, CLOAD = pf, VS = 5 V, VREF =.5 V 3579-3 X mv/div mv/div X 4µs/DIV Figure 49. Small Signal Pulse Response, G =, RLOAD = kω, CLOAD = pf, VS = 5 V, VREF =.5 V 3579-7 X 4µs/DIV Figure 5. Small Signal Pulse Response, G =, RLOAD = kω, CLOAD = pf, VS = 5 V, VREF =.5 V 3579- Rev. B Page 7 of 8
5 SETTLING TIME (µs) 5 SETTLED TO.% SETTLED TO.% SETTLING TIME (µs) SETTLED TO.% SETTLED TO.% 5 5 OUTPUT VOLTAGE STEP SIZE (V) Figure 53. Settling Time vs. Output Voltage Step Size (G = ) ±5 V, VREF = V 3579-43 GAIN (V/V) Figure 54. Settling Time vs. Gain for a V Step, VS = ±5 V, VREF = V 3579-4 Rev. B Page 8 of 8
THEORY OF OPERATION +V S +V S +V S +V S NODE A R G NODE B kω R 4.7kΩ R 4.7kΩ kω kω NODE F A3 +V S OUTPUT +V S +V S NODE C NODE D NODE E +V S +IN J Q C C Q J IN kω REF V PINCH A A V PINCH I VB I Figure 55. Simplified Schematic 3579-6 The AD8 is a JFET input, monolithic instrumentation amplifier based on the classic 3-op amp topology (see Figure 55). Input Transistor J and Input Transistor J are biased at a fixed current so that any input signal forces the output voltages of A and A to change accordingly; the input signal creates a current through RG that flows in R and R such that the outputs of A and A provide the correct, gained signal. Topologically, J, A, and R and J, A, and R can be viewed as precision current feedback amplifiers that have a gain bandwidth of.5 MHz. The common-mode voltage and amplified differential signal from A and A are applied to a difference amplifier that rejects the common-mode voltage but amplifies the differential signal. The difference amplifier employs kω laser-trimmed resistors that result in an in-amp with gain error less than.4%. New trim techniques were developed to ensure that CMRR exceeds 86 db (G = ). Using JFET transistors, the AD8 offers an extremely high input impedance, extremely low bias currents of pa maximum, a low offset current of.6 pa maximum, and no input bias current noise. In addition, input offset is less than 5 μv and drift is less than 5 μv/ C. Ease of use and robustness were considered. A common problem for instrumentation amplifiers is that at high gains, when the input is overdriven, an excessive milliampere input bias current can result and the output can undergo phase reversal. The AD8 has none of these problems; its input bias current is limited to less than μa, and the output does not phase reverse under overdrive fault conditions. Overdriving the input at high gains refers to when the input signal is within the supply voltages but the amplifier cannot output the gained signal. For example, at a gain of, driving the amplifier with V on ±5 V constitutes overdriving the inputs since the amplifier cannot output V. The AD8 has extremely low load-induced nonlinearity. All amplifiers that comprise the AD8 have rail-to-rail output capability for enhanced dynamic range. The input of the AD8 can amplify signals with wide common-mode voltages even slightly lower than the negative supply rail. The AD8 operates over a wide supply voltage range. It can operate from either a single +4.5 V to +36 V supply or a dual ±.5 V to ±8 V. The transfer function of the AD8 is 49.4 kω G R G Users can easily and accurately set the gain using a single, standard resistor. Because the input amplifiers employ a current feedback architecture, the AD8 gain-bandwidth product increases with gain, resulting in a system that does not suffer as much bandwidth loss as voltage feedback architectures at higher gains. A unique pinout enables the AD8 to meet a CMRR specification of 8 db through 5 khz (G = ). The balanced pinout, shown in Figure 56, reduces parasitics that adversely affect CMRR performance. In addition, the new pinout simplifies board layout because associated traces are grouped together. For example, the gain setting resistor pins are adjacent to the inputs, and the reference pin is next to the output. IN R G R G 3 +IN 4 AD8 +V S TOP VIEW (Not to Scale) Figure 56. Pin Configuration 8 7 6 5 V OUT REF 3579-5 Rev. B Page 9 of 8
GAIN SELECTION Placing a resistor across the RG terminals sets the AD8 gain, which can be calculated by referring to Table 5 or by using the gain equation RG 49.4 kω G Table 5. Gains Achieved Using % Resistors % Standard Table Value of RG (Ω) Calculated Gain 49.9 k.99.4 k 4.984 5.49 k 9.998.6 k 9.93. k 5.4 499. 49 99.4 495. 49.9 99. The AD8 defaults to G = when no gain resistor is used. Gain accuracy is determined by the absolute tolerance of RG. The TC of the external gain resistor increases the gain drift of the instrumentation amplifier. Gain error and gain drift are kept to a minimum when the gain resistor is not used. LAYOUT Careful board layout maximizes system performance. In applications that need to take advantage of the low input bias current of the AD8, avoid placing metal under the input path to minimize leakage current. To maintain high CMRR over frequency, lay out the input traces symmetrically and lay out the traces of the RG resistor symmetrically. Ensure that the traces maintain resistive and capacitive balance; this holds for additional PCB metal layers under the input and RG pins. Traces from the gain setting resistor to the RG pins should be kept as short as possible to minimize parasitic inductance. An example layout is shown in Figure 57 and Figure 58. To ensure the most accurate output, the trace from the REF pin should either be connected to the AD8 local ground (see Figure 59) or connected to a voltage that is referenced to the AD8 local ground. Common-Mode Rejection Ratio (CMRR) The AD8 has high CMRR over frequency giving it greater immunity to disturbances, such as line noise and its associated harmonics, in contrast to typical in-amps whose CMRR falls off around Hz. These in-amps often need common-mode filters at the inputs to compensate for this shortcoming. The AD8 is able to reject CMRR over a greater frequency range, reducing the need for input common-mode filtering. A well-implemented layout helps to maintain the high CMRR over frequency of the AD8. Input source impedance and capacitance should be closely matched. In addition, source resistance and capacitance should be placed as close to the inputs as possible. Grounding The output voltage of the AD8 is developed with respect to the potential on the reference terminal. Care should be taken to tie REF to the appropriate local ground (see Figure 59). In mixed-signal environments, low level analog signals need to be isolated from the noisy digital environment. Many ADCs have separate analog and digital ground pins. Although it is convenient to tie both grounds to a single ground plane, the current traveling through the ground wires and PC board can cause a large error. Therefore, separate analog and digital ground returns should be used to minimize the current flow from sensitive points to the system ground. 3579-3579- Figure 57. Example Layout Top Layer of the AD8 Evaluation Board Figure 58. Example Layout Bottom Layer of the AD8 Evaluation Board Rev. B Page of 8
REFERENCE TERMINAL The reference terminal, REF, is at one end of a kω resistor (see Figure 55). The output of the instrumentation amplifier is referenced to the voltage on the REF terminal; this is useful when the output signal needs to be offset to voltages other than common. For example, a voltage source can be tied to the REF pin to level-shift the output so that the AD8 can interface with an ADC. The allowable reference voltage range is a function of the gain, common-mode input, and supply voltages. The REF pin should not exceed either +VS or VS by more than.5 V. For best performance, especially in cases where the output is not measured with respect to the REF terminal, source impedance to the REF terminal should be kept low, because parasitic resistance can adversely affect CMRR and gain accuracy. POWER SUPPLY REGULATION AND BYPASSING The AD8 has high PSRR. However, for optimal performance, a stable dc voltage should be used to power the instrumentation amplifier. Noise on the supply pins can adversely affect performance. As in all linear circuits, bypass capacitors must be used to decouple the amplifier. A. μf capacitor should be placed close to each supply pin. A μf tantalum capacitor can be used further away from the part (see Figure 59). In most cases, it can be shared by other precision integrated circuits. +V S INPUT BIAS CURRENT RETURN PATH The AD8 input bias current is extremely small at less than pa. Nonetheless, the input bias current must have a return path to common. When the source, such as a transformer, cannot provide a return current path, one should be created (see Figure 6). f HIGH-PASS = πrc C C +V S TRANSFORMER R R AD8 +V S AD8 REF REF +IN IN AD8.µF µf V OUT LOAD REF.µF µf Figure 59. Supply Decoupling, REF and Output Referred to Ground 3579- INPUT PROTECTION AC-COUPLED Figure 6. Creating an IBIAS Path All terminals of the AD8 are protected against ESD. (ESD protection is guaranteed to 4 kv, human body model.) In addition, the input structure allows for dc overload conditions a diode drop above the positive supply and a diode drop below the negative supply. Voltages beyond a diode drop of the supplies cause the ESD diodes to conduct and enable current to flow through the diode. Therefore, an external resistor should be used in series with each of the inputs to limit current for voltages above +Vs. In either scenario, the AD8 safely handles a continuous 6 ma current at room temperature. For applications where the AD8 encounters extreme overload voltages, as in cardiac defibrillators, external series resistors and low leakage diode clamps, such as BAV99Ls, FJHs, or SP7s, should be used. 3579- Rev. B Page of 8
RF INTERFERENCE +5V RF rectification is often a problem in applications where there are large RF signals. The problem appears as a small dc offset voltage. The AD8 by its nature has a 5 pf gate capacitance, CG, at its inputs. Matched series resistors form a natural low-pass filter that reduces rectification at high frequency (see Figure 6). The relationship between external, matched series resistors and the internal gate capacitance is expressed as follows: FilterFreqDIFF πrc G R 4.kΩ R 4.kΩ C C C D C C nf nf nf.µf +IN AD8 µf V OUT REF IN.µF µf FilterFreq CM πrc G 5V Figure 6. RFI Suppression 3579-3 R R +IN IN +5V.µF µf C G AD8 C G REF.µF µf V OUT 5V Figure 6. RFI Filtering Without External Capacitors To eliminate high frequency common-mode signals while using smaller source resistors, a low-pass RC network can be placed at the input of the instrumentation amplifier (see Figure 6). The filter limits the input signal bandwidth according to the following relationship: FilterFreqDIFF πr( CD CC C ) FilterFreq CM πr( CC C G Mismatched CC capacitors result in mismatched low-pass filters. The imbalance causes the AD8 to treat what would have been a common-mode signal as a differential signal. To reduce the effect of mismatched external CC capacitors, select a value of CD greater than times CC. This sets the differential filter frequency lower than the common-mode frequency. ) G 3579-3 COMMON-MODE INPUT VOLTAGE RANGE The common-mode input voltage range is a function of the input range and the outputs of Internal Amplifier A, Internal Amplifier A, and Internal Amplifier A3, the reference voltage, and the gain. Figure 7 to Figure 3 show common-mode voltage ranges for various supply voltages and gains. DRIVING AN ADC An instrumentation amplifier is often used in front of an ADC to provide CMRR and additional conditioning, such as a voltage level shift and gain (see Figure 63). In this example, a.7 nf capacitor and a kω resistor create an antialiasing filter for the AD7685. The.7 nf capacitor also serves to store and deliver the necessary charge to the switched capacitor input of the ADC. The kω series resistor reduces the burden of the.7 nf load from the amplifier. However, large source impedance in front of the ADC can degrade THD. The example shown in Figure 63 is for sub-6 khz applications. For higher bandwidth applications where THD is important, the series resistor needs to be small. At worst, a small series resistor can load the AD8, potentially causing the output to overshoot or ring. In such cases, a buffer amplifier, such as the AD865, should be used after the AD8 to drive the ADC. ±5mV µf.7kω.µf +IN IN +5V AD8 REF +.5V kω.7nf AD7685 ADR435 Figure 63. Driving an ADC in a Low Frequency Application +5V 4.7µF 3579-33 Rev. B Page of 8
APPLICATIONS INFORMATION AC-COUPLED INSTRUMENTATION AMPLIFIER Measuring small signals that are in the noise or offset of the amplifier can be a challenge. Figure 64 shows a circuit that can improve the resolution of small ac signals. The large gain reduces the referred input noise of the amplifier to 4 nv/ Hz. Therefore, smaller signals can be measured because the noise floor is lower. DC offsets that would have been gained by are eliminated from the AD8 output by the integrator feedback network. At low frequencies, the OP77 forces the AD8 output to V. Once a signal exceeds fhigh-pass, the AD8 outputs the amplified input signal..µf R 499Ω +IN IN +V S AD8 REF f HIGH-PASS = πrc C R 5.8kΩ DIFFERENTIAL OUTPUT In certain applications, it is necessary to create a differential signal. New high resolution ADCs often require a differential input. In other cases, transmission over a long distance can require differential processing for better immunity to interference. Figure 65 shows how to configure the AD8 to output a differential signal. An OP77 op amp is used to create a differential voltage. Errors from the op amp are common to both outputs and are thus common mode. Likewise, errors from using mismatched resistors cause a common-mode dc offset error. Such errors are rejected in differential signal processing by differential input ADCs or instrumentation amplifiers. When using this circuit to drive a differential ADC, VREF can be set using a resistor divider from the reference of the ADC to make the output ratiometric with the ADC as shown in Figure 66. µf +V S.µF.µF OP77 +V S.µF µf µf Figure 64. AC-Coupled Circuit V REF 3579-4 Rev. B Page 3 of 8
+5V AMPLITUDE.µF +5V 5V ±5V TIME +IN IN.µF AD8 REF 4.99kΩ V OUT A=+V IN +V REF AMPLITUDE +5.V +.5V +V TIME µf +5V 5V 4.99kΩ 5V.µF OP77.µF +5V AMPLITUDE +5.V V REF +.5V.5V +V TIME Figure 65. Differential Output with Level Shift V OUT B= V IN +V REF 3579-8 +5V.µF ±5V TIME +IN IN.µF +5V µf AD8 REF 4.99kΩ 5V 4.99kΩ 5V.µF OP77 V REF.5V V OUT A=+V IN +V REF TO V TO +5V ADC +5V +5V FROM REFERENCE.µF 4.99kΩ 4.99kΩ nf +5V FROM REFERENCE REF +AIN AIN TO V TO +5V ADC V OUT B= V IN +V REF Figure 66. Configuring the AD8 to Output A Ratiometric, Differential Signal 3579-3 Rev. B Page 4 of 8
ELECTROCARDIOGRAM SIGNAL CONDITIONING The AD8 makes an excellent input amplifier for next generation ECGs. Its small size, high CMRR over frequency, rail-to-rail output, and JFET inputs are well suited for this application. Potentials measured on the skin range from. mv to mv. The AD8 solves many of the typical challenges of measuring these body surface potentials. The high CMRR of the AD8 helps reject common-mode signals that come in the form of line noise or high frequency EMI from equipment in the operating room. Its rail-to-rail output offers a wide dynamic range allowing for higher gains than would be possible using other instrumentation amplifiers. JFET inputs offer a large input capacitance of 5 pf. A natural RC filter is formed reducing high frequency noise when series input resistors are used in front of the AD8 (see the RF Interference section). In addition, the AD8 JFET inputs have ultralow input bias current and no current noise, making it useful for ECG applications where there are often large impedances. The MSOP and the optimal pinout of the AD8 allow smaller footprints and more efficient layout, paving the way for next-generation portable ECGs. Figure 67 shows an example ECG schematic. Following the AD8 is a.33 Hz high-pass filter, formed by the 4.7 μf capacitor and the MΩ resistor, which removes the dc offset that develops between the electrodes. An additional gain of 5, provided by the AD868, makes use of the V to 5 V input range of the ADC. An active, fifth-order, low-pass Bessel filter removes signals greater than approximately 6 Hz. An OP77 buffers, inverts, and gains the common-mode voltage taken at the midpoint of the AD8 gain setting resistors. This rightleg drive circuit helps cancel common-mode signals by inverting the common-mode signal and driving it back into the body. A 499 kω series resistor at the output of the OP77 limits the current driven into the body. C A B 5kΩ.pF kω pf kω.pf +5V 5V 4.9kΩ +5V 4.9kΩ 5V AD8 INSTRUMENTATION AMPLIFIER G=+4 4.kΩ OP77 +5V 5V 5V OP AMPS.5V.8kΩ HIGH-PASS FILTER.33Hz +5V 4.7µF pf.5v G=+5 57.6kΩ MΩ +5V 4kΩ AD868.5V LOW-PASS FIFTH ORDER FILTER AT 57Hz 4kΩ 47nF +5V 9.3kΩ AD868 9.3kΩ 33nF AD868 +5V.5V 33nF.5kΩ 4.99kΩ 4.5kΩ 4.5kΩ 68nF AD868 +5V.5V nf 5Ω.7nF AD7685 ADC REF +5V 4.7µF REFERENCE ADR435 68pF.7kΩ 866kΩ 499kΩ +5V OP77 5V 3579-3 Figure 67. Example ECG Schematic Rev. B Page 5 of 8
OUTLINE DIMENSIONS 3. 3..8 3. 3..8 8 5 4 5.5 4.9 4.65 PIN IDENTIFIER.65 BSC.95.85.75.5.5 COPLANARITY..4.5. MAX 6 5 MAX.3.9 COMPLIANT TO JEDEC STANDARDS MO-87-AA Figure 68. 8-Lead Mini Small Outline Package [MSOP] (RM-8) Dimensions shown in millimeters.8.55.4 79-B ORDERING GUIDE Model, Temperature Range 3 Package Description Package Option Branding AD8ARMZ 4 C to +85 C 8-Lead MSOP RM-8 H AD8ARMZ-RL 4 C to +85 C 8-Lead MSOP, 3" Tape and Reel RM-8 H AD8ARMZ-R7 4 C to +85 C 8-Lead MSOP, 7" Tape and Reel RM-8 H AD8BRMZ 4 C to +85 C 8-Lead MSOP RM-8 HP AD8BRMZ-RL 4 C to +85 C 8-Lead MSOP, 3" Tape and Reel RM-8 HP AD8BRMZ-R7 4 C to +85 C 8-Lead MSOP, 7" Tape and Reel RM-8 HP AD8WARMZ 4 C to +5 C 8-Lead MSOP RM-8 YD AD8WARMZ-RL 4 C to +5 C 8-Lead MSOP, 3" Tape and Reel RM-8 YD AD8WARMZ-R7 4 C to +5 C 8-Lead MSOP, 7" Tape and Reel RM-8 YD Z = RoHS Compliant Part. W = Qualified for Automotive Applications. 3 See the Typical Performance Characteristics section for expected operation from 85 C to 5 C. AUTOMOTIVE PRODUCTS The AD8W models are available with controlled manufacturing to support the quality and reliability requirements of automotive applications. Note that these automotive models may have specifications that differ from the commercial models; therefore, designers should review the Specifications section of this data sheet carefully. Only the automotive grade products shown are available for use in automotive applications. Contact your local Analog Devices account representative for specific product ordering information and to obtain the specific Automotive Reliability reports for these models. Rev. B Page 6 of 8
NOTES Rev. B Page 7 of 8
NOTES 6 Analog Devices, Inc. All rights reserved. Trademarks and registered trademarks are the property of their respective owners. D3579--5/(B) Rev. B Page 8 of 8
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