MP1430 3A, 28V, 385KHz Step-Down Converter
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1 TM MP0 A, 8, 85KHz tep-down Converter TM The Future of Analog IC Technology PRELIMARY RELEAE PECIFICATION UBJECT TO CHANGE DECRIPTION The MP0 is a step-down regulator with an internal Power MOFET. It achieves A continuous output current over a wide input supply range with excellent load and line regulation. Current mode operation provides fast transient response and eases loop stabilization. Fault condition protection includes cycle-by-cycle current limiting and thermal shutdown. Adjustable soft-start reduces the stress on the input source at turn-on. In shutdown mode the regulator draws 0µA of supply current. The MP0 requires a minimum number of readily available external components to complete a A step down DC to DC converter solution. EALUATION BOARD REFERENCE Board Number Dimensions E0DN-00A. X x. Y x 0. Z FEATURE A Output Current Programmable oft-tart 0mΩ Internal Power MOFET witch table with Low ER Output Ceramic Capacitors Up to 95% Efficiency 0µA hutdown Mode Fixed 85KHz Frequency Thermal hutdown Cycle-by-Cycle Over Current Protection Wide 6 to 8 Operating Input Range Output Adjustable from. Under oltage Lockout Available in 8-Pin OIC Package APPLICATION Distributed Power ystems Battery Chargers Pre-Regulator for Linear Regulators Flat Panel Ts et-top Boxes Cigarette Lighter Powered Devices DD/PR Devices MP and The Future of Analog IC Technology are Trademarks of Monolithic Power ystems, Inc. TYPICAL APPLICATION PUT 6 to 8 OFF ON 7 B EN MP0 8 GND 5 C6 (optional) 6 C 8.nF C5 0nF D B0A PUT. A MP0_TAC0 EFFICIENCY (%) Efficiency vs Load Current LOAD CURRENT (ma) MP0_TAC _EC0 MP0 Rev. 0.
2 MP0 A, 8, 85KHz TEP-DOWN CONERTER PRELIMARY RELEAE PECIFICATION UBJECT TO CHANGE PACKAGE REFERENCE B GND EXPOED PAD ON BACKIDE CONNECT TO P TOP IEW EN MP0_PD0_OIC8N Part Number* Package Temperature MP0DN OIC8N (Exposed Pad) 0 C to +85 C * For Tape & Reel, add suffix Z (eg. MP0DN Z) For Lead Free, add suffix LF (eg. MP0DN LF Z) ABOLUTE MAXIMUM RATG () upply oltage to 0 witch oltage to + 0. Boost oltage B to + 6 All Other Pins to +6 Junction Temperature...50 C Lead Temperature...60 C torage Temperature C to 50 C Recommended Operating Conditions () Input oltage... 6 to 8 Ambient Operating Temp... 0 C to +85 C Thermal Resistance () θ JA θ JC OIC8N (w/exposed Pad) C/W Notes: ) Exceeding these ratings may damage the device. ) The device is not guaranteed to function outside of its operating conditions. ) Measured on approximately square of oz copper. ELECTRICAL CHARACTERITIC, T A +5 C, unless otherwise noted. Parameter ymbol Condition Min Typ Max Units hutdown upply Current EN µa upply Current EN.6,..0. ma Feedback oltage 6 8 < Error Amplifier oltage Gain A EA 00 / Error Amplifier Transconductance G EA I ±0µA µa/ High ide witch On Resistance R D(ON) 0 mω Low ide witch On Resistance R D(ON) 0 Ω High ide witch Leakage Current EN 0, µa Current Limit..5 A Current ense to Transconductance G C 6. A/ Oscillation Frequency f OC KHz hort Circuit Oscillation Frequency f OC KHz Maximum Duty Cycle D MAX.0 90 % Minimum Duty Cycle D M.5 0 % MP0 Rev. 0.
3 I L A/Div. I L A/Div. I L A/Div. ELECTRICAL CHARACTERITIC (continued), T A +5 C, unless otherwise noted. MP0 A, 8, 85KHz TEP-DOWN CONERTER PRELIMARY RELEAE PECIFICATION UBJECT TO CHANGE Parameter ymbol Condition Min Typ Max Units EN Threshold oltage Enable Pull Up Current EN µa Under oltage Lockout Threshold Rising..6.9 Under oltage Lockout Threshold Hysteresis 0 m oft tart Period C 0.µF 0 ms Thermal hutdown 60 C TYPICAL PERFORMANCE CHARACTERITIC Refer to Typical Application chematic on Page FEEDBACK OLTAGE () Feedback oltage vs Temperature TEMPERATURE ( C) MP0-TPC0 PEAK CURRENT LIMIT (A) Peak Current Limit vs Temperature TEMPERATURE ( C) TEMPERATURE ( C) MP0-TPC0 OCILLATION FREQUENCY (KHz) Oscillation Frequency vs Temperature MP0-TPC0 oft-tart Waveforms Turn Off Waveforms Load Transient Waveforms /Div. /Div. 00m/Div. ms/div. MP0-TPC0 MP0-TPC05,., A - A TEP MP0-TPC-06 MP0 Rev. 0.
4 MP0 A, 8, 85KHz TEP-DOWN CONERTER PRELIMARY RELEAE PECIFICATION UBJECT TO CHANGE TYPICAL PERFORMANCE CHARACTERITIC (continued) Refer to Typical Application chematic on Page witching Waveforms MP0-TPC07 I L A/Div. 0m/Div. 00m/Div. 0/Div. EFFICIENCY (%) Efficiency vs Load Current LOAD CURRENT (ma) MP0_TPC08 EFFICIENCY (%) Efficiency vs Load Current LOAD CURRENT (ma) MP0 _TPC09 P FUNCTION Pin # Name Description B High-ide Gate Drive Boost Input. B supplies the drive for the high-side N-Channel MOFET switch. Connect a 0nF or greater capacitor from to B to power the high side switch. Power Input. supplies the power to the IC, as well as the step-down converter switches. Drive with a 6 to 8 power source. Bypass to GND with a suitably large capacitor to eliminate noise on the input to the IC. ee Input Capacitor section. Power witching Output. is the switching node that supplies power to the output. Connect the output LC filter from to the output load. Note that a capacitor is required from to B to power the high-side switch. GND Ground. (Note: Connect the exposed pad on backside to Pin ). 5 Feedback Input. senses the output voltage to regulate that voltage. Drive with a resistive voltage divider from the output voltage. The feedback threshold is.. ee etting the Output oltage section. Compensation Node. is used to compensate the regulation control loop. Connect a series 6 RC network from to GND to compensate the regulation control loop. In some cases, an additional capacitor from to GND is required. ee Compensation section. 7 EN Enable Input. EN is a digital input that turns the regulator on or off. Drive EN high to turn on the regulator, drive EN low to turn it off. An Under oltage Lockout (ULO) function can be implemented by the addition of a resistor divider from to GND. For complete low current shutdown its needs to be less than 0.7. For automatic startup, leave EN unconnected. 8 oft-tart Control Input. controls the soft-start period. Connect a capacitor from to GND to set the soft-start period. A 0.µF capacitor sets the soft-start period to 0ms. To disable the soft-start feature, leave unconnected. MP0 Rev. 0.
5 OPERATION MP0 A, 8, 85KHz TEP-DOWN CONERTER PRELIMARY RELEAE PECIFICATION UBJECT TO CHANGE TERNAL REGULATOR CURRENT ENE AMPLIFIER + 5 OCILLATOR LOPE 0/85KHz CLK + + Q M B EN HUTDOWN ARATOR LOCK ARATOR R Q CURRENT ARATOR.8 M./ GND FREQUENCY FOLDBACK ARATOR ERROR AMPLIFIER 6 8 MP0_BD0 Figure Functional Block Diagram The MP0 is a current-mode step-down regulator. It regulates input voltages from 6 to 8 down to an output voltage as low as., and is able to supply up to A of load current. The MP0 uses current-mode control to regulate the output voltage. The output voltage is measured at through a resistive voltage divider and amplified through the internal error amplifier. The output current of the transconductance error amplifier is presented at where a network compensates the regulation control system. The voltage at is compared to the switch current measured internally to control the output voltage. The converter uses an internal N-Channel MOFET switch to step-down the input voltage to the regulated output voltage. ince the MOFET requires a gate voltage greater than the input voltage, a boost capacitor connected between and B drives the gate. The capacitor is internally charged while is low. An internal 0Ω switch from to GND is used to insure that is pulled to GND when is low to fully charge the B.capacitor. MP0 Rev
6 APPLICATION FORMATION ONENT ELECTION etting the Output oltage The output voltage is set using a resistive voltage divider from the output voltage to pin. The voltage divider divides the output voltage down to the feedback voltage by the ratio: R R + R Where is the feedback voltage and is the output voltage. Thus the output voltage is: R + R. R A typical value for R can be as high as 00kΩ, but a typical value is 0kΩ. Using that value, R is determined by: R 8.8 (.)(kω) For example, for a. output voltage, R is 0kΩ, and R is 7kΩ. Inductor The inductor is required to supply constant current to the output load while being driven by the switched input voltage. A larger value inductor will result in less ripple current that will result in lower output ripple voltage. However, the larger value inductor will have a larger physical size, higher series resistance, and/or lower saturation current. A good rule for determining the inductance to use is to allow the peak-to-peak ripple current in the inductor to be approximately 0% of the maximum switch current limit. Also, make sure that the peak inductor current is below the maximum switch current limit. The inductance value can be calculated by: L f I L MP0 A, 8, 85KHz TEP-DOWN CONERTER PRELIMARY RELEAE PECIFICATION UBJECT TO CHANGE Where is the input voltage, f is the 85KHz switching frequency, and I L is the peak-topeak inductor ripple current. Choose an inductor that will not saturate under the maximum inductor peak current. The peak inductor current can be calculated by: I LP I LOAD + f Where I LOAD is the load current. L Table lists a number of suitable inductors from various manufacturers. The choice of which style inductor to use mainly depends on the price vs. size requirements and any EMI requirement. Table Inductor election Guide endor/ Model Core Type Package Dimensions Core (mm) Material W L H umida CR75 Open Ferrite CDH7 Open Ferrite CDRH5D8 hielded Ferrite CDRH5D8 hielded Ferrite CDRH6D8 hielded Ferrite CDRH0R hielded Ferrite Toko D5LC Type A hielded Ferrite D75C hielded Ferrite D0C hielded Ferrite D0FL Open Ferrite Coilcraft DO08 Open Ferrite DO6 Open Ferrite MP0 Rev
7 Output Rectifier Diode The output rectifier diode supplies the current to the inductor when the high-side switch is off. To reduce losses due to the diode forward voltage and recovery times, use a chottky diode. Choose a diode whose maximum reverse voltage rating is greater than the maximum input voltage, and whose current rating is greater than the maximum load current. Table lists example chottky diodes and manufacturers. Table Diode election Guide Diode oltage/current Rating Manufacturer K 0, A Diodes Inc. K 0, A Diodes Inc. B0 0, A Diodes Inc. B0 0, A Diodes Inc. MBR0 0, A On emiconductor MBR0 0, A On emiconductor Input Capacitor The input current to the step-down converter is discontinuous, therefore a capacitor is required to supply the AC current to the step-down converter while maintaining the DC input voltage. Use low ER capacitors for the best performance. Ceramic capacitors are preferred, but tantalum or low-er electrolytic capacitors may also suffice. ince the input capacitor absorbs the input switching current it requires an adequate ripple current rating. The RM current in the input capacitor can be estimated by: I C I LOAD MP0 A, 8, 85KHz TEP-DOWN CONERTER PRELIMARY RELEAE PECIFICATION UBJECT TO CHANGE The worst-case condition occurs at, where: I C I LOAD For simplification, choose the input capacitor whose RM current rating greater than half of the maximum load current. The input capacitor can be electrolytic, tantalum or ceramic. When using electrolytic or tantalum capacitors, a small, high quality ceramic capacitor, i.e. 0.µF, should be placed as close to the IC as possible. When using ceramic capacitors, make sure that they have enough capacitance to provide sufficient charge to prevent excessive voltage ripple at input. The input voltage ripple caused by capacitance can be estimated by: ILOAD f C MP0 Rev Where C is the input capacitance value. Output Capacitor The output capacitor is required to maintain the DC output voltage. Ceramic, tantalum, or low ER electrolytic capacitors are recommended. Low ER capacitors are preferred to keep the output voltage ripple low. The output voltage ripple can be estimated by: f L R ER + 8 f C Where L is the inductor value, C O is the output capacitance value, and R ER is the equivalent series resistance (ER) value of the output capacitor. In the case of ceramic capacitors, the impedance at the switching frequency is dominated by the capacitance. The output voltage ripple is mainly caused by the capacitance. For simplification, the output voltage ripple can be estimated by: 8 f L C O In the case of tantalum or electrolytic capacitors, the ER dominates the impedance at the switching frequency. For simplification, the output ripple can be approximated to: R f L ER The characteristics of the output capacitor also affect the stability of the regulation system. The MP0 can be optimized for a wide range of capacitance and ER values. O
8 Compensation Components MP0 employs current mode control for easy compensation and fast transient response. The system stability and transient response are controlled through the pin. pin is the output of the internal transconductance error amplifier. A series capacitor-resistor combination sets a pole-zero combination to control the characteristics of the control system. The DC gain of the voltage feedback loop is given by: A DC RLOAD GC A EA MP0 A, 8, 85KHz TEP-DOWN CONERTER PRELIMARY RELEAE PECIFICATION UBJECT TO CHANGE Where A EA is the error amplifier voltage gain, 00/, G C is the current sense transconductance, 5.9A/, and R LOAD is the load resistor value. The system has two poles of importance. One is due to the compensation capacitor (C) and the output resistor of error amplifier, and the other is due to the output capacitor and the load resistor. These poles are located at: f f P P GEA π C A π C R O EA LOAD Where G EA is the error amplifier transconductance, 800µA/. The system has one zero of importance, due to the compensation capacitor (C) and the compensation resistor (R). This zero is located at: π C f Z R The system may have another zero of importance, if the output capacitor has a large capacitance and/or a high ER value. The zero, due to the ER and capacitance of the output capacitor, is located at: f ER π C R O ER In this case (as shown in Figure ), a third pole set by the compensation capacitor (C6) and the compensation resistor (R) is used to compensate the effect of the ER zero on the loop gain. This pole is located at: π C6 f P R The goal of compensation design is to shape the converter transfer function to get a desired loop gain. The system crossover frequency where the feedback loop has the unity gain is important. Lower crossover frequencies result in slower line and load transient responses, while higher crossover frequencies could cause system unstable. A good rule of thumb is to set the crossover frequency to approximately one-tenth of the switching frequency. witching frequency for the MP0 is 85KHz, so the desired crossover frequency is around 8KHz. Table lists the typical values of compensation components for some standard output voltages with various output capacitors and inductors. The values of the compensation components have been optimized for fast transient responses and good stability at given conditions. MP0 Rev
9 Table Compensation alues for Typical Output oltage/capacitor Combinations L C O R C C6.8.7µH 00µF 5.6kΩ.nF None Ceramic µH 7µF Ceramic.9kΩ 5.6nF None µH 5 0-5µH 5- µh µfx Ceramic µfx Ceramic µfx Ceramic.8.7µH 00µF P-CAP µH µH 5 0-5µH µH µH 5 0-5µH 5- µh 7µF P-CAP 7µF P-CAP 7µF P CAP 560µF Al. 0mΩ ER 560µF Al 0mΩ ER 70µF Al. 0mΩ ER 0µF Al. 0mΩ ER MP0 A, 8, 85KHz TEP-DOWN CONERTER PRELIMARY RELEAE PECIFICATION UBJECT TO CHANGE 5.6kΩ 8.nF None 7.5kΩ 0nF None 0kΩ.nF None 5.6kΩ.nF 00pF.7kΩ 5.6nF None 6.8kΩ 0nF None 0kΩ 0nF None 0kΩ 5.6nF.5nF 0kΩ 8.nF.5nF 5kΩ 5.6nF nf 5kΩ.7nF 90pF To optimize the compensation components for conditions not listed in Table, the following procedure can be used.. Choose the compensation resistor (R) to set the desired crossover frequency. Determine the R value by the following equation: π CO fc R G G EA C Where f C is the desired crossover frequency (which typically has a value no higher than 8KHz).. Choose the compensation capacitor (C) to achieve the desired phase margin. For applications with typical inductor values, setting the compensation zero, f Z, below one forth of the crossover frequency provides sufficient phase margin. Determine the C value by the following equation: C > π R Where, R is the compensation resistor value and f C is the desired crossover frequency, 8KHz.. Determine if the second compensation capacitor (C6) is required. It is required if the ER zero of the output capacitor is located at less than half of the 85KHz switching frequency, or the following relationship is valid: π C O R f C f < ER Where, C O is the output capacitance value, R ER is the ER value of the output capacitor, and f is the 85KHz switching frequency. If this is the case, then add the second compensation capacitor (C6) to set the pole f P at the location of the ER zero. Determine the C6 value by the equation: C C6 O R R ER Where, C O is the output capacitance value, R ER is the ER value of the output capacitor, and R is the compensation resistor. External Bootstrap Diode It is recommended that an external bootstrap diode be added when the system has a 5 fixed input or the power supply generates a 5 output. This helps improve the efficiency of the regulator. The bootstrap diode can be a low cost one such as 8 or BAT5. MP0 B 5 0nF MP0_F0 Figure External Bootstrap Diode This diode is also recommended for high duty cycle operation (when >65%) and high output voltage ( >) applications. MP0 Rev
10 TYPICAL APPLICATION CIRCUIT PUT 6 to 8 MP0 A, 8, 85KHz TEP-DOWN CONERTER PRELIMARY RELEAE PECIFICATION UBJECT TO CHANGE C5 0nF OFF ON 7 8 EN GND MP0 C6 (optional) B 5 6 C.nF D B0A PUT.5 A MP0_F0 Figure MP0 with AX 7µF, 6. Ceramic Output Capacitor PUT 6 to 8 C5 0nF OFF ON 7 8 EN GND MP0 C6 (optional) B 5 6 C.nF D B0A PUT.5 A MP0_F0 Figure MP0 with Panasonic 7µF, 6. pecial Polymer Output Capacitor MP0 Rev
11 MP0 A, 8, 85KHz TEP-DOWN CONERTER PRELIMARY RELEAE PECIFICATION UBJECT TO CHANGE PACKAGE FORMATION OIC8N (EXPOED PAD) P IDENT. 0.9(5.80) 0.(6.00) 0.50(.80) 0.57(.000) (0.9) (0.9) NOTE 0.0(0.0) 0.00(0.508) 0.050(.70)BC EE DETAIL "A" 0.0(0.80) 0.00(0.508) x 5o 0.05(.50) 0.068(.70) 0.89(.800) 0.97(5.00) 0.09(.50) 0.060(.5) 0.00(0.00) 0.00(0.0) EATG PLANE 0 o -8 o 0.06(0.0) DETAIL "A" 0.050(.70) NOTE: ) Control dimension is in inches. Dimension in bracket is millimeters. ) Exposed Pad;.55+/- 0.5mm x.8 +/- 0.mm. Recommended older Board Area:.80mm x.8mm 0.7mm (6.6mil ) NOTICE: The information in this document is subject to change without notice. Please contact MP for current specifications. Users should warrant and guarantee that third party Intellectual Property rights are not infringed upon when integrating MP products into any application. MP will not assume any legal responsibility for any said applications. MP0 Rev. 0.
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