Receiver synchronisation based on a single dummy frame for DVB-S2/S2X beam hopping systems

Transcription

1 Receiver synchronisation based on a single dummy frame for DVB-S2/S2X beam hopping systems Xavier Giraud Cabinet NOVACOM giraud.novacom@wanadoo.fr Guy Lesthievent CNES guy.lesthievent@cnes.fr Hugo Méric CNES hugo.meric@cnes.fr Abstract We study the receiver synchronisation in a DVB- S2/S2X beam hopping system. In such a scenario, each beam is illuminated during defined temporal windows. As a consequence, the receivers do not receive a continuous signal which strongly disturbs their synchronisation. To tackle this problem without using a specific format, we introduce a dedicated dummy frame with a synchronisation field that enables the receiver to lock with one frame even with poor channel conditions (a signal-tonoise ratio down to -10 db). This solution is fully compliant with the existing standards. Through simulations, we present the performance of our scheme and demonstrate its effectiveness for DVB-S2/S2X systems. I. INTRODUCTION Very high throughput satellites combined with multi-beams systems provide a significant increase of the available capacity. However on-board resources (especially high power amplifiers) are limited due to consumption, mass and dissipation. Moreover, the traffic demand is time varying and differs between beams. One solution to properly allocate the resources and solve previous constraints is beam hopping. To that end, beam hopping proposes a temporal allocation of the resources by illuminating the beams in various temporal windows (thus avoiding a complicated frequency allocation). First studies regarding beam hopping dated back to 2006 [1]. Since then, the literature has been growing [2] [9]. Previous works cover the payload architecture [1] [4], [6], the system performance combined with resource allocation algorithms [1], [3] [7] and the receiver synchronisation [8], [9]. In this work, we study the receiver synchronisation. This means the frame, frequency, phase and timing synchronisations as the receiver needs to lock after a period without signal. All previous works studying synchronisation for beam hopping systems rely on the super-frame format introduced in DVB-S2X [10, Annex E] and depicted in Fig. 1a (we also remind the DVB-S2/S2X framing in Fig. 1b). In [8], [9], the authors use this new framing as a solution to synchronisation issues in beam hopping and very-low signal-to-noise ratio (VL-SNR) modes. They present synchronisation performance such as false alarm and missed detection probabilities. Even if the super-frame presents some benefits, its adoption by the satellite community is not that simple as it has many impacts on the transmitter and the receiver: special header (not backward-compatible with DVB-S2), long and fixed framing size (the super-frame lasts more than 6 ms for R s < 100 MBauds), limited granularity, insufficient guard symbols for switching and system uncertainty, hardware complexity, etc. Before going any further, we shortly discuss the impact of the super-frame (or any possible framing) length in a beam hopping system. Even at 500 MBauds, the super-frame lasts more than 1 ms as shown in Fig. 1c. Thus the gap between two consecutive illuminations may be quite long. A long period FEC encoding 270 symb. 450 symb. SOSF SFFI symb. Ressource allocation (format specific) symb. (a) Super-frame (optionnal) format composed of: start of super-frame, super-frame format indicator and the resource (several PLFRAMES as depicted in Fig. 1b and pilots) BBFRAME FECFRAME Bit mapping to symbols Frame duration [s] XFECFRAME PL framing PLFRAME 80 bits BB header Slot 1 Slot 2 PL header Data field BBFRAME K BCH Slot 1 90 symb. 90 symb. bits Slot S Slot 16 BCH FEC Pilot block 36 symb. LDPC FEC N LDPC K BCH bits (b) DVB-S2/S2X framing (mandatory) Dummy Super QPSK 8PSK Slot S 16APSK 32APSK Bits Symbols R s [MBaud] (c) Duration of normal frame ( encoded bits) with pilots Fig. 1: DVB-S2/S2X framing

2 Gateway Dummy frames for switching and synchronisation A timing synchronisation exists between the gateways and the satellite. DUMMY Dummy frame for padding Gateway antennas SATELLITE HPA Beam antennas DUMMY GROUND RECEIVERS Gateway GROUND TRANSMITTERS HPA BHSYnc Fig. 2: Use of a single dummy frame, noted, to manage switching and receiver synchronisation in a beam hopping system. If several time slots are dedicated to the same beam, the frame is skipped. without signal impacts the synchronisation at the physical layer, the delay at the transport layer and even the application in case of video transmission. To avoid long period without signal, a shorter framing may be considered. Let consider a framing of around symbols. Using the MODCOD distribution presented in [11], the average PLFRAME length is roughly symbols and the framing can carry only 8 frames, which may not be enough. In the current work, we aim at providing an alternative to the super-frame by proposing a dedicated dummy frame, called, with a synchronisation field (thus compatible with the DVB-S2/S2X standard). The idea to rely on dummy frame was introduced in [12] to address synchronisation issues with standard modems. However the previous scheme requires around 20 dummy frames; in our current work a single dummy frame is sufficient thanks to its synchronisation field. We illustrate our idea in Fig. 2: the synchronisation between the gateways and the payload (necessary in a beam hopping scenario, but out of the scope of this paper) enables the gateways to insert a dedicated dummy frame, the, in the transmitted stream to facilitate the switching and the receiver synchronisation. At 500 MBauds, one dummy frame lasts 6.7 µs (with a 90 symbols PLHEADER). Assuming that the ferrite switches commutation time is less than 2 µs [13], [14] and that the system uncertainty is roughly 0.5 µs, a synchronisation field can be included in a dummy frame to help the receiver. Thus a single dummy frame deals with the switching and the receiver synchronisation. As depicted in Fig. 2, classical dummy frames may still be used for padding as in classical DVB-S2/S2X systems (as suggested in [10, Section 5.5.1]) and the frame is necessary only when a commutation occurs. If several consecutive time slots are allocated to the same beam, only one is relevant. The main contribution of our work, presented in Section II, is the design of a synchronisation field in the dummy frame and the corresponding receiver architecture. This enables the receiver to synchronise with a unique dummy frame even in a beam hopping scenario with poor channel condition (down to - 10 db). This constitutes an alternative to the super-frame introduced in [10, Annex E]. Moreover, very few modifications are to be done at transmitter side as our proposal is fully compliant with DVB-S2/S2X. In Section III, we evaluate the performance of our scheme through simulations. We conclude this paper by concluding remarks and perspectives in Section IV. II. PROPOSED SCHEME frame. Fig. 3a presents the frame structure. The frame is divided in three parts. The first part is the PLHEADER, as defined in the DVB-S2/S2X standard [16], with 90 or 180 symbols. Then there are N c symbols that will manage the switching duration and the system uncertainty as discussed earlier. Finally, a synchronisation field of 924 symbols is inserted at the end of the frame to help the receiver after a period without signal. We depict the structure of the synchronisation field in Fig. 3b. This field has 33 blocks of 28 symbols each. We use a spreading factor of 28 to obtain a processing gain of 14.5 db. Among the 33 blocks, 17 blocks (P i with 0 i 16) serve to estimate the carrier frequency offset. The remaining 16 blocks (CW i with 0 i 15) are encoded with a Reed- Muller code of parameter [4, 16] where the least significant bit 90 or 180 symb. 28 PLH* Nc symb. Dummy switching area (a) frame 924 symb. Sync. field P 0 CW 0 P 1 CW 1 P 15 CW 15 P (b) Structure of the synchronisation field Fig. 3: frame and synchronisation field

3 Frequency offset estimation Detection confirmation MAX MAX Decoded CW FFT (128) FWHT (16) Zero padding Step 2 Frequency offset correction Step 3 P CW P CW DL CW P (33) Receiver state machine 28xOSF 28xOSF 28xOSF 28xOSF DL 0 (32x28xOSF) 28xOSF SS0 SS1 SS2 SS3 SS 3x Samples Mean power: P 2 16 multipliers Adder (16) Step 1 ABS Score Primary detection alarm Fig. 4: Receiver architecture to detect and decode the frame is forced to zero to ensure that the XOR of two consecutive bits is 1. These blocks carry 3 information bits. We assume that the pilot symbols are equal to e i π 4 and the coded symbols are equal to ±e i π 4. We apply a scrambling sequence SS i (0 i 32) to the entire synchronisation field. Receiver architecture. The synchronisation after a period without signal concerns both timing and frequency offsets and relies a unique word detection. Even more, clock and frequency reference drifts in the user terminal must be considered for a cold start. The receiver must work with an oversampling factor (OSF) with respect to the channel symbol rate R s. In practice, OSF is greater or equal to 2 (we use 2 in the simulations). The general receiver architecture is depicted in Fig. 4. The detection and estimation of the various parameters work in three steps. In Step 1, the objective is to detect the frame. To that end, the samples are stored in a delay line (DL 0 in Fig. 4) and we compute the correlations with the sequences SS i (0 i 31). The correlations are stored in the delay line 1. At the same time, we add the correlation products for a differential detection. This operation requires 16 complex multipliers on 28 symbols. This choice has been driven to reuse the VL-SNR correlator (16 56) hardware. If the score at the bottom of Fig. 4 is greater than a threshold, a primary alarm is declared and we go into Step 2. In Step 2, the values in DL 1 does not change (the switches between DL 0 and DL 1 are openend). A last correlation is done to obtain P 16. We can see in Fig. 4 that the receiver state machine controls the last switch). From these 33 correlations, we use the correlations corresponding to the P i (0 i 16) to obtain a coarse frequency offset estimation. This requires a FFT of size 128 where zero padding has been used. The FFT also confirms the synchronisation (in order to decrease the false alarm probability). The receiver is now aware of the frequency offset and can enter Step 3. In Step 3, we start by correcting the correlation results CW i (0 i 15). The corrected values are sent to a Fast Walsh Hadamard Transform (FWHT) to decode the three information bits carried in the frame. The maximum value of the FWHT is also helpful to confirm the synchronisation and exclude false alarms. The proposed architecture has a low complexity in order to facilitate its hardware implementation. Indeed, the complexity drove the synchronisation field design. We will now study its performance.

4 Standard deviation CFO CRB (L=924) CRB (L=476) Timing offset = 0 Standard deviation T/T CRB (L=896, roll off=0.2) Timing offset = (a) Carrier frequency offset estimation accuracy (b) Timing offset estimation accuracy SNR estimation [db] 10 5 Timing offset = (c) SNR estimation accuracy Probability (FA threshold=t/4) 10 0 False alarm Missed detection (d) False alarm and missed detection probabilities Fig. 5: Synchronisation performance of the proposed scheme (T is the symbol duration) III. SYNCHRONISATION PERFORMANCE Frequency synchronisation. The first result evaluates the frequency estimation accuracy. To that end, we compare the standard deviation of the normalized carrier frequency offset (defined as f T where f is the carrier frequency offset and T is the symbol period) with the Cramer-Rao bound for a unique word of length L symbols [15] given by E[( ˆf f) 2 ] CRB(f) = 3 2π 2 1 L(L 2 1) 1 E s N 0, (1) where E is the expected value and ˆf is the frequency estimation. Our simulator work with two samples per symbols, thus a processing gain of 2 is necessary to compute the standard deviation. Moreover, we assume that the normalized CFO is lower than Fig. 5a presents the results for various timing offsets. We remind that the frequency estimation uses 17 fields of 28 symbols each (P X with 0 X 16 in Fig. 3b), resulting in 476 symbols. However, we also depict the Cramer-Rao bound for a unique word of 924 symbols (the entire length of the synchronisation field). The results point out that the detection is almost optimal when the receiver is synchronised in time. Thus we verify that the FFT is an optimal estimator. When the timing offset increases, the frequency error also increases and reaches its maximum at T/4, where T is the symbol duration. For very low SNR, typically below -11 db, the results have a bias as the missed detections are not taken into account (and the missed detection probability becomes significant). Timing synchronisation. As for the frequency estimation, we compute the standard deviation of the timing estimation error and compare it to the Cramer-Rao bound [15] given by E[(ˆτ τ) 2 ] CRB(τ) = 1 2g α(0) 1 L 1 E s N 0, (2) where ˆτ is the timing estimation and g α is the raised cosine function with roll-off α (α = 0.2 in the simulations). Fig. 5b presents the results. The estimation is excellent when the timing offset is low. We obtain a loss of 2.5 db compared to the Cramer-Rao bound when the timing offset is equal to T/4 (worst case). SNR estimation. Fig. 5c shows the SNR estimation accuracy. The results are excellent when the timing offset is low. Note that the estimation variance increases when the SNR decreases, even for small timing offsets. Finally, we see that the SNR estimation degrades significantly at large SNR if the timing offset is large. The estimation error may impact the phase tracking loop (if the loop parameters depends on the SNR) and the LLR computation. If the receiver performance is degraded, a second SNR

5 estimator may be installed after the timing synchronisation. This is part of future work. False alarm/missed detection. Finally, we present the false alarm and missed detection probabilities in Fig. 5d. We compute the different detection thresholds empirically. A false alarm is returned when the estimated sampling instant is greater than T/4 which corresponds to a worst case. The results exhibit a false alarm and a missed detection probabilities below at -10 db. The performance is similar to the results presented in [9]. Setting different detection thesholds will change the false alarm and missed detection rates. However, the important performance is the frame error rate at the receiver. By reaching a false alarm and missed detection rates of about at -9.8 db, we comply with the DVB-S2X objective in terms of frame error rate (the targeted performance is ). IV. CONCLUSION In this work, we introduce a dedicated synchronisation field in dummy frames for helping the receiver synchronisation in a beam hopping systems. By carefully designing the receiver algorithms, we demonstrate the effectiveness of our scheme through simulations. The main advantage is that a unique dummy frame enables to deal with the switching and the receiver synchronisation, while being compatible with the DVB-S2/S2X standard. Future work will extend the current results in three directions. First, we will complete the performance evaluation by obtaining frame error rate performance for various MOD- CODS from very-low to large SNR. Then we are currently investigating the impact of beam interference, in case of frequency reuse, with our solution. We rely on different scrambling sequences in neighboring beams to fight againt these interferences. Finally, we plan to test our proposal on a testbed. REFERENCES [7] J. Lei and M. 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