Narrowband Microstrip Filter Design With NI AWR Microwave Office
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1 Narrowband Microstrip Filter Design With NI AWR Microwave Office Daniel G. Swanson, Jr. DGS Associates, LLC Boulder, CO
2 Narrowband Microstrip Filters There are many topologies we can choose from. The interdigital filter has been very popular. But it has some design and fabrication challenges. D. G. Swanson, Jr., Narrow-Band Microwave Filter Design, IEEE Microwave Magazine, vol. 8, no. 5, pp , Oct Microstrip Filter Design 2
3 Microstrip Interdigital y x +y metal pattern misalignment Resonators 1, 3, 5 get longer Resonators 2 & 4 get shorter The filter is badly mistuned Standard metal pattern to via alignment spec is +/- 2 mils Interdigital at X-band requires something like +/- 0.2 mils Microstrip Filter Design 3
4 Microstrip Combline Microstrip interdigital topology Has been a workhorse for many years Very compact in terms of wavelengths Very sensitive to absolute via placement Very sensitive to alignment of metal pattern to vias Y-axis misalignment rapidly detunes filter Microstrip combline topology Has not been studied in detail Also very compact in terms of wavelengths True combline requires loading capacitors and extra vias Microstrip combline is not pure TEM, allows longer resonator All resonators are grounded at the same end Y-axis misalignment should only shift center frequency Microstrip Filter Design 4
5 Conventional Combline deg Resonators are typically 50 to 60 degrees long for moderate bandwidths. For octave band filters resonators may be in the 30 degree range. For narrow band filters resonators may be in the 70 to 80 degree range. Some form of capacitive loading is used to achieve resonance. If the medium is pure TEM, 90 degree long combline resonators do not couple. Microstrip Filter Design 5
6 Microstrip Combline If we want to build a microstrip combline it is tempting to adopt the conventional topology. But we need an extra set of vias for the capacitive loading. And we need to accurately realize the capacitive loading, possibly with an interdigital capacitor structure to get significant loading. Microstrip Filter Design 6
7 10% BW Microstrip Combline L = 94 mils 15 mil alumina 25 mil wide resonators What if we arbitrarily throw away the capacitive top loading? Our first assumption is that resonators will be close to 90 degrees long and we may not get much coupling. This assumes the vias are ideal short circuits, which of course they are not. It also assumes a pure TEM environment, which microstrip is not. In fact, we can port tune this structure to be a 10% bandwidth filter. Microstrip Filter Design 7
8 Port Tuned Response Microstrip Filter Design 8
9 10% BW Microstrip Combline deg After optimization, the printed parts of the resonators are 73 to 77 degrees long, depending on the assumed reference plane for the vias. We have some capacitive loading due to the open end fringing. And we have significant loading due to the finite inductance of the vias. There is also some mutual inductance between the vias. Compared to the conventional approach, this microstrip combline is both bottom loaded and top loaded. Microstrip Filter Design 9
10 Combline Filter Fabrication Absolute via placement is still a problem with the combline Metalized slot replaces vias Misalignment variables Slot or pattern Y-axis shift Slot or pattern XY rotation Efficient thin-film process Applied Thin-Film Products EM modeling is simpler and faster without vias Metalized slot Microstrip Filter Design 10
11 Microstrip Combline Example N = 5 Microstrip Interdigital Center Frequency: 2.44 GHz Bandwidth: 244 MHz (10%) Insertion Loss: < 2 db Return Loss: 20 db (.044 db ripple) Microstrip Filter Design 11
12 Design Flow Estimate order of filter and stopband rejection Choose waveguide channel dimensions Distributed filters couple to the waveguide channel Build model of proposed resonator (with loss) Compute available Qu Estimate insertion loss Build Kij design curve (no loss) Build Qex design curve (no loss) Build model of complete filter and apply port tuning Use port tuning corrections to refine filter dimensions Do final run of filter with loss turned on Verify insertion loss in passband Verify rejection in stopbands Microstrip Filter Design 12
13 Chebyshev Lowpass Prototype Chebyshev Lowpass Prototype: db ripple, 20 db return loss, 1.22 VSWR N g 0 g 1 g 2 g 3 g 4 g 5 g 6 g 7 g 8 g 9 g 10 g 1 -g N N is the lowpass or bandpass filter order. The g i s are frequency and impedance scaled values for a lowpass filter with a cutoff frequency of = 1 radian and a return loss of 20 db. Any given passband ripple / return loss level requires a unique table. Other tables are available in the literature or the g i s can be computed. Microstrip Filter Design 13
14 Microstrip Qu EMSight AWRDE V11 25mil (.635mm) thick alumina assumed r = mil by 435mil (1.27mm by 11.05mm) 600 mil 150 mil 25 mil Vertical via metal Microstrip Filter Design 14
15 Microstrip Qu From Group Delay 230 Microstrip Filter Design 15
16 Midband Insertion Loss Chebyshev Lowpass Prototype: db ripple, 20 db return loss, 1.22 VSWR N g 0 g 1 g 2 g 3 g 4 g 5 g 6 g 7 g 8 g 9 g 10 g 1 -g N Loss( N gi f0 i f0) 1.23 db f Q u Loss will be higher at the band edges. Microstrip Filter Design 16
17 Dishal s Method As early as 1951, Milton Dishal [2] recognized that any narrow band, lumped element or distributed bandpass filter could be described by three fundamental variables: the synchronous tuning frequency, f 0 the couplings between adjacent resonators, K r,r+1 the singly loaded or external Q, Q ex The K ij set the bandwidth of the filter and the Q ex sets the return loss level. For any narrowband filter (<10% bandwidth) we can compute the required K ij and Q ex from the Chebyshev lowpass prototype. The K and Q concept is universal and can be applied to any lumped element or distributed filter topology or technology [4,5]. Microstrip Filter Design 17
18 Microstrip Filter Design 18 Definition of Kij and Qex ) ( f f f BW f f f g g BW g g f f f K BW g g f f g g f Q j i j i ij ex f 1 = bandpass filter lower equal ripple frequency f 2 = bandpass filter upper equal ripple frequency f 0 = bandpass filter center frequency BW = percentage bandwidth g i = prototype element value for element i Note: Equations assume Qu is infinite.
19 Our Filter: N = 5, BW = 10% Chebyshev Lowpass Prototype: db ripple, 20 db return loss, 1.22 VSWR N g 0 g 1 g 2 g 3 g 4 g 5 g 6 g 7 g 8 g 9 g 10 g 1 -g N K K Q 1,2 2,3 ex BW g g 1 2 g0 g BW g BW 1 2 g Microstrip Filter Design 19
20 Computing Spacings and Tap Height Our resonator geometry is now fixed. We have enough Qu to meet the insertion loss goal. We have goals for the Kij s and Qex Now we need to compute the spacings between resonators and the tap height. Microstrip Filter Design 20
21 Computing Coupling Coefficients Compute coupling coefficient as function of spacing between resonators. Lossless model Faster No corrections to Kij Via ports for tuning in our circuit simulator MoM mesh may not be perfectly symmetrical Faster than making geometry changes in the EM model EMSight AWRDE V11 Microstrip Filter Design 21
22 Computing Coupling Coefficients EMSight AWRDE V mil 600 mil 25 mil Vertical via metal Microstrip Filter Design 22
23 Extracting Coupling Coefficients Loosely couple with transformers. We want to force synchronous tuning. At resonance: mag( im( Y (1,1))) 0 mag( im( Y (2,2))) 0 Microstrip Filter Design 23
24 Extracting Coupling Coefficients -30 db min Coupling Coefficient Coupling Bandwidth f f 2 2 f 0 f f MHz Microstrip Filter Design 24
25 Coupling Curve: Fit in Mathcad Spacing K K mil 150 mil 25 mil Microstrip Filter Design 25
26 Computing Qex Tune to center frequency at Port 2. Measure reflected group delay at Port 1. Tap height sets the return loss level of our filter. Note this resonator is longer than the resonators used to compute couplings. Microstrip Filter Design 26
27 Port Tuned Reflected Delay Q Q ex ex Tap_Height = 93 mils 2 f (GHz) td (ns) Microstrip Filter Design 27
28 Qex Curve: Fit in Mathcad Tap Height Delay Delay 600 mil 150 mil 25 mil Microstrip Filter Design 28
29 First Iteration Geometry S1 = 31 mils S2 = 47 mils L1 = 442 mils L2 = 437 mils Tap Height = 97 mils Microstrip Filter Design 29
30 Default Meshing Microstrip Filter Design 30
31 First Iteration Response 4350 Unknowns AFS Sweep 15 Frequencies 600 mil 150 mil 25 mil Microstrip Filter Design 31
32 Arbitrary Channel Height Change 100 mil 600 mil 25 mil Microstrip Filter Design 32
33 Internal Ports for Port Tuning Internal nodes External port Tuning element Low error Very effective for frequency tuning Limited to lumped elements by the transformer How do we tune couplings? Microstrip Filter Design 33
34 Impact of Internal Ports Microstrip Filter Design 34
35 Port Tuning With Internal Ports Custom symbol Dummy element Coupled inductor array zero tuning = +20 ph Mutual couplings M ij K L i ij 0 1 K ij L i 1 L j Mutual couplings tune EM circuit couplings Add negative offset inductors so coupled L s don t go negative. Microstrip Filter Design 35
36 Port Tuning with EQR_OPT General purpose optimizers may work fine for low order filters, but they can be inefficient for more complex filters. EQR_OPT_MWO is a dedicated optimizer for microwave filters. It finds an exact equal ripple response with a very small number of iterations. It communicates with Microwave Office via the COM interface. It works on any Chebyshev filter that can be defined in Microwave Office. We can also use it to port tune an S-parameter file from any EM simulator. Microstrip Filter Design 36
37 Second Iteration: Port Tuned X X X X X X EM simulation frequencies Microstrip Filter Design 37
38 What Do The Tunings Tell Us? Center resonator tuning is almost perfect (remember zero is +20 ph) The outer resonators want to be longer The first and last gaps want to be smaller The inner gaps want to be larger Return loss tells us the tap position wants to move down very slightly The resonator and coupling tunings will interact The general strategy is to go after the largest errors at each step Next step: Resonators 1, 2, 4, 5 each one mil longer Move tap down one mil Microstrip Filter Design 38
39 Third Iteration Microstrip Filter Design 39
40 Fourth Iteration Resonator tunings are all pretty close The first and last gaps want to be smaller The inner gaps want to be larger Return loss is perfect Next step: First and last gaps one mil smaller Inner gaps one mil larger Microstrip Filter Design 40
41 Fifth Iteration Coupling corrections are small and in the numerical noise (note opposite signs) Resonator tunings have shifted We need less than a full one mil change in resonator length and resonator spacing. Next step: Fine tune open ends Fine tune couplings Microstrip Filter Design 41
42 Fine Tunings Reso 1 Reso 2 Reso 3 Add and subtract bits of metal at the open ends to fine tune the resonators. We have to go back and forth a little between frequency and coupling adjustments. Adding or subtracting metal at the base of the resonators fine tunes the coupling. Microstrip Filter Design 42
43 Final Tuning If we set the tunings to zero and see very little movement in the response we are done. Next step is to remove the tuning ports and do a two port analysis of the filter. Microstrip Filter Design 43
44 Two Port EM Simulation Microstrip Filter Design 44
45 Two Port EM Simulation Microstrip Filter Design 45
46 Summary Dishal s K and Q method leads us to a simple design flow for narrowband filters. We can modernize the method by using EMSight to build the Kij and Qex design curves that we need. We can then build a complete model of our filter in EMSight, port tune it and get a very good prediction of performance. These virtual prototypes in our EM simulator avoid the time and expense of multiple hardware prototypes. Experience has shown that we can rely on the EM simulator models. Microstrip Filter Design 46
47 References [1] R. Levy, R. Snyder and G. Matthaei, Design of Microwave Filters, IEEE Trans. Microwave Theory Tech., vol. MTT-50, pp , March [2] M. Dishal, Alignment and adjustment of synchronously tuned multiple resonate circuit filters, Proc IRE, vol. 30, pp , Nov [3] M. Dishal, A simple design procedure for small percentage bandwidth round-rod interdigital filters, IEEE Trans. Microwave Theory Tech., vol. MTT-13, pp , Sept [4] J. Wong, Microstrip tapped-line filter design, IEEE Trans. Microwave Theory Tech., vol. MTT-27, pp , Jan [5] D. G. Swanson, Jr., Narrow-Band Microwave Filter Design, IEEE Microwave Magazine, vol. 8, no. 5, pp , Oct [6] D. G. Swanson, Jr., Corrections to Narrow-Band Microwave Filter Design, IEEE Microwave Magazine, vol. 9, no. 1, p. 116, Feb Microstrip Filter Design 48
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