Coherent Lightwave Systems

Size: px
Start display at page:

Download "Coherent Lightwave Systems"

Transcription

1 Fiber-Optic Communications Systems, Third Edition. Govind P. Agrawal Copyright 2002 John Wiley & Sons, Inc. ISBNs: (Hardback); (Electronic) Chapter 10 Coherent Lightwave Systems The lightwave systems discussed so far are based on a simple digital modulation scheme in which an electrical bit stream modulates the intensity of an optical carrier inside the optical transmitter and the optical signal transmitted through the fiber link is incident directly on an optical receiver, which converts it to the original digital signal in the electrical domain. Such a scheme is referred to as intensity modulation with direct detection (IM/DD). Many alternative schemes, well known in the context of radio and microwave communication systems [1] [6], transmit information by modulating the frequency or the phase of the optical carrier and detect the transmitted signal by using homodyne or heterodyne detection techniques. Since phase coherence of the optical carrier plays an important role in the implementation of such schemes, such optical communication systems are called coherent lightwave systems. Coherent transmission techniques were studied during the 1980s extensively [7] [16]. Commercial deployment of coherent systems, however, has been delayed with the advent of optical amplifiers although the research and development phase has continued worldwide. The motivation behind using the coherent communication techniques is two-fold. First, the receiver sensitivity can be improved by up to 20 db compared with that of IM/DD systems. Second, the use of coherent detection may allow a more efficient use of fiber bandwidth by increasing the spectral efficiency of WDM systems. In this chapter we focus on the design of coherent lightwave systems. The basic concepts behind coherent detection are discussed in Section In Section 10.2 we present new modulation formats possible with the use of coherent detection. Section 10.3 is devoted to synchronous and asynchronous demodulation schemes used by coherent receivers. The bit-error rate (BER) for various modulation and demodulation schemes is considered in Section Section 10.5 focuses on the degradation of receiver sensitivity through mechanisms such as phase noise, intensity noise, polarization mismatch, fiber dispersion, and reflection feedback. The performance aspects of coherent lightwave systems are reviewed in Section 10.6 where we also discuss the status of such systems at the end of

2 10.1. BASIC CONCEPTS 479 Figure 10.1: Schematic illustration of a coherent detection scheme Basic Concepts Local Oscillator The basic idea behind coherent detection consists of combining the optical signal coherently with a continuous-wave (CW) optical field before it falls on the photodetector (see Fig. 10.1). The CW field is generated locally at the receiver using a narrowlinewidth laser, called the local oscillator (LO), a term borrowed from the radio and microwave literature. To see how the mixing of the received optical signal with the LO output can improve the receiver performance, let us write the optical signal using complex notation as E s = A s exp[ i(ω 0 t + φ s )], (10.1.1) where ω 0 is the carrier frequency, A s is the amplitude, and φ s is the phase. The optical field associated with the local oscillator is given by a similar expression, E LO = A LO exp[ i(ω LO t + φ LO )], (10.1.2) where A LO, ω LO, and φ LO represent the amplitude, frequency, and phase of the local oscillator, respectively. The scalar notation is used for both E s and E LO after assuming that the two fields are identically polarized (polarization-mismatch issues are discussed later in Section ). Since a photodetector responds to the optical intensity, the optical power incident at the photodetector is given by P = K E s + E LO 2, where K is a constant of proportionality. Using Eqs. (10.1.1) and (10.1.2), where P(t)=P s + P LO + 2 P s P LO cos(ω IF t + φ s φ LO ), (10.1.3) P s = KA 2 s, P LO = KA 2 LO, ω IF = ω 0 ω LO. (10.1.4) The frequency ν IF ω IF /2π is known as the intermediate frequency (IF). When ω 0 ω LO, the optical signal is demodulated in two stages; its carrier frequency is first converted to an intermediate frequency ν IF (typically GHz) before the signal is demodulated to the baseband. It is not always necessary to use an intermediate frequency.

3 480 CHAPTER 10. COHERENT LIGHTWAVE SYSTEMS In fact, there are two different coherent detection techniques to choose from, depending on whether or not ω IF equals zero. They are known as homodyne and heterodyne detection techniques Homodyne Detection In this coherent-detection technique, the local-oscillator frequency ω LO is selected to coincide with the signal-carrier frequency ω 0 so that ω IF = 0. From Eq. (10.1.3), the photocurrent (I = RP, where R is the detector responsivity) is given by I(t)=R(P s + P LO )+2R P s P LO cos(φ s φ LO ). (10.1.5) Typically, P LO P s, and P s + P LO P LO. The last term in Eq. (10.1.5) contains the information transmitted and is used by the decision circuit. Consider the case in which the local-oscillator phase is locked to the signal phase so that φ s = φ LO. The homodyne signal is then given by I p (t)=2r P s P LO. (10.1.6) The main advantage of homodyne detection is evident from Eq. (10.1.6) if we note that the signal current in the direct-detection case is given by I dd (t)=rp s (t). Denoting the average optical power by P s, the average electrical power is increased by a factor of 4P LO / P s with the use of homodyne detection. Since P LO can be made much larger than P s, the power enhancement can exceed 20 db. Although shot noise is also enhanced, it is shown later in this section that homodyne detection improves the signal-to-noise ratio (SNR) by a large factor. Another advantage of coherent detection is evident from Eq. (10.1.5). Because the last term in this equation contains the signal phase explicitly, it is possible to transmit information by modulating the phase or frequency of the optical carrier. Direct detection does not allow phase or frequency modulation, as all information about the signal phase is lost. The new modulation formats for coherent systems are discussed in Section A disadvantage of homodyne detection also results from its phase sensitivity. Since the last term in Eq. (10.1.5) contains the local-oscillator phase φ LO explicitly, clearly φ LO should be controlled. Ideally, φ s and φ LO should stay constant except for the intentional modulation of φ s. In practice, both φ s and φ LO fluctuate with time in a random manner. However, their difference φ s φ LO can be forced to remain nearly constant through an optical phase-locked loop. The implementation of such a loop is not simple and makes the design of optical homodyne receivers quite complicated. In addition, matching of the transmitter and local-oscillator frequencies puts stringent requirements on the two optical sources. These problems can be overcome by the use of heterodyne detection, discussed next Heterodyne Detection In the case of heterodyne detection the local-oscillator frequency ω LO is chosen to differ form the signal-carrier frequency ω 0 such that the intermediate frequency ω IF is

4 10.1. BASIC CONCEPTS 481 in the microwave region (ν IF 1 GHz). Using Eq. (10.1.3) together with I = RP, the photocurrent is now given by I(t)=R(P s + P LO )+2R P s P LO cos(ω IF t + φ s φ LO ). (10.1.7) Since P LO P s in practice, the direct-current (dc) term is nearly constant and can be removed easily using bandpass filters. The heterodyne signal is then given by the alternating-current (ac) term in Eq. (10.1.7) or by I ac (t)=2r P s P LO cos(ω IF t + φ s φ LO ). (10.1.8) Similar to the case of homodyne detection, information can be transmitted through amplitude, phase, or frequency modulation of the optical carrier. More importantly, the local oscillator still amplifies the received signal by a large factor, thereby improving the SNR. However, the SNR improvement is lower by a factor of 2 (or by 3 db) compared with the homodyne case. This reduction is referred to as the heterodynedetection penalty. The origin of the 3-dB penalty can be seen by considering the signal power (proportional to the square of the current). Because of the ac nature of I ac, the average signal power is reduced by a factor of 2 when I 2 ac is averaged over a full cycle at the intermediate frequency (recall that the average of cos 2 θ over θ is 1 2 ). The advantage gained at the expense of the 3-dB penalty is that the receiver design is considerably simplified because an optical phase-locked loop is no longer needed. Fluctuations in both φ s and φ LO still need to be controlled using narrow-linewidth semiconductor lasers for both optical sources. However, as discussed in Section , the linewidth requirements are quite moderate when an asynchronous demodulation scheme is used. This feature makes the heterodyne-detection scheme quite suitable for practical implementation in coherent lightwave systems Signal-to-Noise Ratio The advantage of coherent detection for lightwave systems can be made more quantitative by considering the SNR of the receiver current. For this purpose, it is necessary to extend the analysis of Section 4.4 to the case of heterodyne detection. The receiver current fluctuates because of shot noise and thermal noise. The variance σ 2 of current fluctuations is obtained by adding the two contributions so that where σ 2 = σ 2 s + σ 2 T, (10.1.9) σ 2 s = 2q(I + I d ) f, σ 2 T =(4k B T /R L )F n f. ( ) The notation used here is the same as in Section 4.4. The main difference from the analysis of Section 4.4 occurs in the shot-noise contribution. The current I in Eq. ( ) is the total photocurrent generated at the detector and is given by Eq. (10.1.5) or Eq. (10.1.7), depending on whether homodyne or heterodyne detection is employed. In practice, P LO P s, and I in Eq. ( ) can be replaced by the dominant term RP LO for both cases.

5 482 CHAPTER 10. COHERENT LIGHTWAVE SYSTEMS The SNR is obtained by dividing the average signal power by the average noise power. In the heterodyne case, it is given by SNR = I2 ac σ 2 = 2R 2 P s P LO 2q(RP LO + I d ) f + σt 2. ( ) In the homodyne case, the SNR is larger by a factor of 2 if we assume that φ s = φ LO in Eq. (10.1.5). The main advantage of coherent detection can be seen from Eq. ( ). Since the local-oscillator power P LO can be controlled at the receiver, it can be made large enough that the receiver noise is dominated by shot noise. More specifically, σs 2 σ T 2 when P LO σt 2 /(2qR f ). ( ) Under the same conditions, the dark-current contribution to the shot noise is negligible (I d RP LO ). The SNR is then given by SNR R P s q f = η P s hν f, ( ) where R = ηq/hν was used from Eq. (4.1.3). The use of coherent detection allows one to achieve the shot-noise limit even for p i n receivers whose performance is generally limited by thermal noise. Moreover, in contrast with the case of avalanche photodiode (APD) receivers, this limit is realized without adding any excess shot noise. It is useful to express the SNR in terms of the number of photons, N p, received within a single bit. At the bit rate B, the signal power P s is related to N p as P s = N p hνb. Typically, f B/2. By using these values of P s and f in Eq. ( ), the SNR is given by a simple expression SNR = 2ηN p. ( ) In the case of homodyne detection, SNR is larger by a factor of 2 and is given by SNR = 4ηN p. Section 10.4 discusses the dependence of the BER on SNR and shows how receiver sensitivity is improved by the use of coherent detection Modulation Formats As discussed in Section 10.1, an important advantage of using the coherent detection techniques is that both the amplitude and the phase of the received optical signal can be detected and measured. This feature opens up the possibility of sending information by modulating either the amplitude, or the phase, or the frequency of an optical carrier. In the case of digital communication systems, the three possibilities give rise to three modulation formats known as amplitude-shift keying (ASK), phase-shift keying (PSK), and frequency-shift keying (FSK) [1] [6]. Figure 10.2 shows schematically the three modulation formats for a specific bit pattern. In the following subsections we consider each format separately and discuss its implementation in practical lightwave systems.

6 10.2. MODULATION FORMATS 483 Figure 10.2: ASK, PSK, and FSK modulation formats for a specific bit pattern shown on the top ASK Format The electric field associated with an optical signal can be written as [by taking the real part of Eq. (10.1.1)] E s (t)=a s (t)cos[ω 0 t + φ s (t)]. (10.2.1) In the case of ASK format, the amplitude A s is modulated while keeping ω 0 and φ s constant. For binary digital modulation, A s takes one of the two fixed values during each bit period, depending on whether 1 or 0 bit is being transmitted. In most practical situations, A s is set to zero during transmission of 0 bits. The ASK format is then called on off keying (OOK) and is identical with the modulation scheme commonly used for noncoherent (IM/DD) digital lightwave systems. The implementation of ASK for coherent systems differs from the case of the direct-detection systems in one important aspect. Whereas the optical bit stream for direct-detection systems can be generated by modulating a light-emitting diode (LED) or a semiconductor laser directly, external modulation is necessary for coherent communication systems. The reason behind this necessity is related to phase changes that

7 484 CHAPTER 10. COHERENT LIGHTWAVE SYSTEMS invariably occur when the amplitude A s (or the power) is changed by modulating the current applied to a semiconductor laser (see Section 3.5.3). For IM/DD systems, such unintentional phase changes are not seen by the detector (as the detector responds only to the optical power) and are not of major concern except for the chirp-induced power penalty discussed in Section The situation is entirely different in the case of coherent systems, where the detector response depends on the phase of the received signal. The implementation of ASK format for coherent systems requires the phase φ s to remain nearly constant. This is achieved by operating the semiconductor laser continuously at a constant current and modulating its output by using an external modulator (see Section 3.6.4). Since all external modulators have some insertion losses, a power penalty incurs whenever an external modulator is used; it can be reduced to below 1 db for monolithically integrated modulators. As discussed in Section 3.64, a commonly used external modulator makes use of LiNbO 3 waveguides in a Mach Zehnder (MZ) configuration [17]. The performance of external modulators is quantified through the on off ratio (also called extinction ratio) and the modulation bandwidth. LiNbO 3 modulators provide an on off ratio in excess of 20 and can be modulated at speeds up to 75 GHz [18]. The driving voltage is typically 5 V but can be reduced to near 3 V with a suitable design. Other materials can also be used to make external modulators. For example, a polymeric electro-optic MZ modulator required only 1.8 V for shifting the phase of a 1.55-µm signal by π in one of the arms of the MZ interferometer [19]. Electroabsorption modulators, made using semiconductors, are often preferred because they do not require the use of an interferometer and can be integrated monolithically with the laser (see Section 3.6.4). Optical transmitters with an integrated electroabsorption modulator capable of modulating at 10 Gb/s were available commercially by 1999 and are used routinely for IM/DD lightwave systems [20]. By 2001, such integrated modulators exhibited a bandwidth of more than 50 GHz and had the potential of operating at bit rates of up to 100 Gb/s [21]. They are likely to be employed for coherent systems as well PSK Format In the case of PSK format, the optical bit stream is generated by modulating the phase φ s in Eq. (10.2.1) while the amplitude A s and the frequency ω 0 of the optical carrier are kept constant. For binary PSK, the phase φ s takes two values, commonly chosen to be 0 and π. Figure 10.2 shows the binary PSK format schematically for a specific bit pattern. An interesting aspect of the PSK format is that the optical intensity remains constant during all bits and the signal appears to have a CW form. Coherent detection is a necessity for PSK as all information would be lost if the optical signal were detected directly without mixing it with the output of a local oscillator. The implementation of PSK requires an external modulator capable of changing the optical phase in response to an applied voltage. The physical mechanism used by such modulators is called electrorefraction. Any electro-optic crystal with proper orientation can be used for phase modulation. A LiNbO 3 crystal is commonly used in practice. The design of LiNbO 3 -based phase modulators is much simpler than that of an amplitude modulator as a Mach Zehnder interferometer is no longer needed, and

8 10.2. MODULATION FORMATS 485 a single waveguide can be used. The phase shift δφ occurring while the CW signal passes through the waveguide is related to the index change δn by the simple relation δφ =(2π/λ )(δn)l m, (10.2.2) where l m is the length over which index change is induced by the applied voltage. The index change δ n is proportional to the applied voltage, which is chosen such that δφ = π. Thus, a phase shift of π can be imposed on the optical carrier by applying the required voltage for the duration of each 1 bit. Semiconductors can also be used to make phase modulators, especially if a multiquantum-well (MQW) structure is used. The electrorefraction effect originating from the quantum-confinement Stark effect is enhanced for a quantum-well design. Such MQW phase modulators have been developed [22] [27] and are able to operate at a bit rate of up to 40 Gb/s in the wavelength range µm. Already in 1992, MQW devices had a modulation bandwidth of 20 GHz and required only 3.85 V for introducing a π phase shift when operated near 1.55 µm [22]. The operating voltage was reduced to 2.8 V in a phase modulator based on the electroabsorption effect in a MQW waveguide [23]. A spot-size converter is sometimes integrated with the phase modulator to reduce coupling losses [24]. The best performance is achieved when a semiconductor phase modulator is monolithically integrated within the transmitter [25]. Such transmitters are quite useful for coherent lightwave systems. The use of PSK format requires that the phase of the optical carrier remain stable so that phase information can be extracted at the receiver without ambiguity. This requirement puts a stringent condition on the tolerable linewidths of the transmitter laser and the local oscillator. As discussed later in Section , the linewidth requirement can be somewhat relaxed by using a variant of the PSK format, known as differential phase-shift keying (DPSK). In the case of DPSK, information is coded by using the phase difference between two neighboring bits. For instance, if φ k represents the phase of the kth bit, the phase difference φ = φ k φ k 1 is changed by π or 0, depending on whether kth bit is a 1 or 0 bit. The advantage of DPSK is that the transmittal signal can be demodulated successfully as long as the carrier phase remains relatively stable over a duration of two bits FSK Format In the case of FSK modulation, information is coded on the optical carrier by shifting the carrier frequency ω 0 itself [see Eq. (10.2.1)]. For a binary digital signal, ω 0 takes two values, ω 0 + ω and ω 0 ω, depending on whether a 1 or 0 bit is being transmitted. The shift f = ω/2π is called the frequency deviation. The quantity 2 f is sometimes called tone spacing, as it represents the frequency spacing between 1 and 0 bits. The optical field for FSK format can be written as E s (t)=a s cos[(ω 0 ± ω)t + φ s ], (10.2.3) where + and signs correspond to 1 and 0 bits. By noting that the argument of cosine can be written as ω 0 t +(φ s ± ωt), the FSK format can also be viewed as a kind of

9 486 CHAPTER 10. COHERENT LIGHTWAVE SYSTEMS PSK modulation such that the carrier phase increases or decreases linearly over the bit duration. The choice of the frequency deviation f depends on the available bandwidth. The total bandwidth of a FSK signal is given approximately by 2 f + 2B, where B is the bit rate [1]. When f B, the bandwidth approaches 2 f and is nearly independent of the bit rate. This case is often referred to as wide-deviation or wideband FSK. In the opposite case of f B, called narrow-deviation or narrowband FSK, the bandwidth approaches 2B. The ratio β FM = f /B, called the frequency modulation (FM) index, serves to distinguish the two cases, depending on whether β FM 1orβ FM 1. The implementation of FSK requires modulators capable of shifting the frequency of the incident optical signal. Electro-optic materials such as LiNbO 3 normally produce a phase shift proportional to the applied voltage. They can be used for FSK by applying a triangular voltage pulse (sawtooth-like), since a linear phase change corresponds to a frequency shift. An alternative technique makes use of Bragg scattering from acoustic waves. Such modulators are called acousto-optic modulators. Their use is somewhat cumbersome in the bulk form. However, they can be fabricated in compact form using surface acoustic waves on a slab waveguide. The device structure is similar to that of an acousto-optic filter used for wavelength-division multiplexing (WDM) applications (see Section 8.3.1). The maximum frequency shift is typically limited to below 1 GHz for such modulators. The simplest method for producing an FSK signal makes use of the direct-modulation capability of semiconductor lasers. As discussed in Section 3.5.2, a change in the operating current of a semiconductor laser leads to changes in both the amplitude and frequency of emitted light. In the case of ASK, the frequency shift or the chirp of the emitted optical pulse is undesirable. But the same frequency shift can be used to advantage for the purpose of FSK. Typical values of frequency shifts are 1 GHz/mA. Therefore, only a small change in the operating current ( 1 ma) is required for producing the FSK signal. Such current changes are small enough that the amplitude does not change much from from bit to bit. For the purpose of FSK, the FM response of a distributed feedback (DFB) laser should be flat over a bandwidth equal to the bit rate. As seen in Fig. 10.3, most DFB lasers exhibit a dip in their FM response at a frequency near 1 MHz [28]. The reason is that two different physical phenomena contribute to the frequency shift when the device current is changed. Changes in the refractive index, responsible for the frequency shift, can occur either because of a temperature shift or because of a change in the carrier density. The thermal effects contribute only up to modulation frequencies of about 1 MHz because of their slow response. The FM response decreases in the frequency range MHz because the thermal contribution and the carrier-density contribution occur with opposite phases. Several techniques can be used to make the FM response more uniform. An equalization circuit improves uniformity but also reduces the modulation efficiency. Another technique makes use of transmission codes which reduce the low-frequency components of the data where distortion is highest. Multisection DFB lasers have been developed to realize a uniform FM response [29] [35]. Figure 10.3 shows the FM response of a two-section DFB laser. It is not only uniform up to about 1 GHz, but its modulation efficiency is also high. Even better performance is realized by using three-section

10 10.3. DEMODULATION SCHEMES 487 Figure 10.3: FM response of a typical DFB semiconductor laser exhibiting a dip in the frequency range MHz. (After Ref. [12]; c 1988 IEEE; reprinted with permission.) DBR lasers described in Section in the context of tunable lasers. Flat FM response from 100 khz to 15 GHz was demonstrated [29] in 1990 in such lasers. By 1995, the use of gain-coupled, phase-shifted, DFB lasers extended the range of uniform FM response from 10 khz to 20 GHz [33]. When FSK is performed through direct modulation, the carrier phase varies continuously from bit to bit. This case is often referred to as continuous-phase FSK (CPFSK). When the tone spacing 2 f is chosen to be B/2(β FM = 1 2 ), CPFSK is also called minimum-shift keying (MSK) Demodulation Schemes As discussed in Section 10.1, either homodyne or heterodyne detection can be used to convert the received optical signal into an electrical form. In the case of homodyne detection, the optical signal is demodulated directly to the baseband. Although simple in concept, homodyne detection is difficult to implement in practice, as it requires a local oscillator whose frequency matches the carrier frequency exactly and whose phase is locked to the incoming signal. Such a demodulation scheme is called synchronous and is essential for homodyne detection. Although optical phase-locked loops have been developed for this purpose, their use is complicated in practice. Heterodyne detection simplifies the receiver design, as neither optical phase locking nor frequency matching of the local oscillator is required. However, the electrical signal oscillates rapidly at microwave frequencies and must be demodulated from the IF band to the baseband using techniques similar to those developed for microwave communication systems [1] [6]. Demodulation can be carried out either synchronously or asynchronously. Asynchronous demodulation is also called incoherent in the radio communication literature. In the optical communication literature, the term coherent detection is used in a wider sense. A lightwave system is called coherent as long as it uses a local oscillator irrespective of the demodulation technique used to convert the IF signal to baseband frequencies. This section focuses on the synchronous and asynchronous demodulation schemes for heterodyne systems.

11 488 CHAPTER 10. COHERENT LIGHTWAVE SYSTEMS Figure 10.4: Block diagram of a synchronous heterodyne receiver Heterodyne Synchronous Demodulation Figure 10.4 shows a synchronous heterodyne receiver schematically. The current generated at the photodiode is passed through a bandpass filter (BPF) centered at the intermediate frequency ω IF. The filtered current in the absence of noise can be written as [see Eq. (10.1.8)] I f (t)=i p cos(ω IF t φ), (10.3.1) where I p = 2R P s P LO and φ = φ LO φ s is the phase difference between the local oscillator and the signal. The noise is also filtered by the BPF. Using the in-phase and out-of-phase quadrature components of the filtered Gaussian noise [1], the receiver noise is included through I f (t)=(i p cosφ + i c )cos(ω IF t)+(i p sinφ + i s )sin(ω IF t), (10.3.2) where i c and i s are Gaussian random variables of zero mean with variance σ 2 given by Eq. (10.1.9). For synchronous demodulation, I f (t) is multiplied by cos(ω IF t) and filtered by a low-pass filter. The resulting baseband signal is I d = I f cos(ω IF t) = 1 2 (I p cosφ + i c ), (10.3.3) where angle brackets denote low-pass filtering used for rejecting the ac components oscillating at 2ω IF. Equation (10.3.3) shows that only the in-phase noise component affects the performance of synchronous heterodyne receivers. Synchronous demodulation requires recovery of the microwave carrier at the intermediate frequency ω IF. Several electronic schemes can be used for this purpose, all requiring a kind of electrical phase-locked loop [36]. Two commonly used loops are the squaring loop and the Costas loop. A squaring loop uses a square-law device to obtain a signal of the form cos 2 (ω IF t) that has a frequency component at 2ω IF. This component can be used to generate a microwave signal at ω IF Heterodyne Asynchronous Demodulation Figure 10.5 shows an asynchronous heterodyne receiver schematically. It does not require recovery of the microwave carrier at the intermediate frequency, resulting in a much simpler receiver design. The filtered signal I f (t) is converted to the baseband by

12 10.3. DEMODULATION SCHEMES 489 Figure 10.5: Block diagram of an asynchronous heterodyne receiver. using an envelope detector, followed by a low-pass filter. The signal received by the decision circuit is just I d = I f, where I f is given by Eq. (10.3.2). It can be written as I d = I f =[(I p cosφ + i c ) 2 +(I p sinφ + i s ) 2 ] 1/2. (10.3.4) The main difference is that both the in-phase and out-of-phase quadrature components of the receiver noise affect the signal. The SNR is thus degraded compared with the case of synchronous demodulation. As discussed in Section 10.4, sensitivity degradation resulting from the reduced SNR is quite small (about 0.5 db). As the phasestability requirements are quite modest in the case of asynchronous demodulation, this scheme is commonly used for coherent lightwave systems. The asynchronous heterodyne receiver shown in Fig requires modifications when the FSK and PSK modulation formats are used. Figure 10.6 shows two demodulation schemes. The FSK dual-filter receiver uses two separate branches to process the 1 and 0 bits whose carrier frequencies, and hence the intermediate frequencies, are different. The scheme can be used whenever the tone spacing is much larger than the bit rates, so that the spectra of 1 and 0 bits have negligible overlap (wide-deviation FSK). The two BPFs have their center frequencies separated exactly by the tone spacing so that each BPF passes either 1 or 0 bits only. The FSK dual-filter receiver can be thought of as two ASK single-filter receivers in parallel whose outputs are combined before reaching the decision circuit. A single-filter receiver of Fig can be used for FSK demodulation if its bandwidth is chosen to be wide enough to pass the entire bit stream. The signal is then processed by a frequency discriminator to identify 1 and 0 bits. This scheme works well only for narrow-deviation FSK, for which tone spacing is less than or comparable to the bit rate (β FM 1). Asynchronous demodulation cannot be used in the case the PSK format because the phase of the transmitter laser and the local oscillator are not locked and can drift with time. However, the use of DPSK format permits asynchronous demodulation by using the delay scheme shown in Fig. 10.6(b). The idea is to multiply the received bit stream by a replica of it that has been delayed by one bit period. The resulting signal has a component of the form cos(φ k φ k 1 ), where φ k is the phase of the kth bit, which can be used to recover the bit pattern since information is encoded in the phase difference φ k φ k 1. Such a scheme requires phase stability only over a few bits and can be implemented by using DFB semiconductor lasers. The delay-demodulation

13 490 CHAPTER 10. COHERENT LIGHTWAVE SYSTEMS Figure 10.6: (a) Dual-filter FSK and (b) DPSK asynchronous heterodyne receivers. scheme can also be used for CPFSK. The amount of delay in that case depends on the tone spacing and is chosen such that the phase is shifted by π for the delayed signal Bit-Error Rate The preceding three sections have provided enough background material for calculating the bit-error rate (BER) of coherent lightwave systems. However, the BER, and hence the receiver sensitivity, depend on the modulation format as well as on the demodulation scheme used by the coherent receiver. The section considers each case separately Synchronous ASK Receivers Consider first the case of heterodyne detection. The signal used by the decision circuit is given by Eq. (10.3.3). The phase φ generally varies randomly because of phase fluctuations associated with the transmitter laser and the local oscillator. As discussed in Section 10.5, the effect of phase fluctuations can be made negligible by using semiconductor lasers whose linewidth is a small fraction of the bit rate. Assuming this to be the case and setting φ = 0 in Eq. (10.3.2), the decision signal is given by I d = 1 2 (I p + i c ), (10.4.1)

14 10.4. BIT-ERROR RATE 491 where I p 2R(P s P LO ) 1/2 takes values I 1 or I 0 depending on whether a 1 or 0 bit is being detected. Consider the case I 0 = 0 in which no power is transmitted during the 0 bits. Except for the factor of 1 2 in Eq. (10.4.1), the situation is analogous to the case of direct detection discussed in Section 4.5. The factor of 1 2 does not affect the BER since both the signal and the noise are reduced by the same factor, leaving the SNR unchanged. In fact, one can use the same result [Eq. (4.5.9)], BER = 1 2 erfc ( Q 2 ), (10.4.2) where Q is given by Eq. (4.5.10) and can be written as Q = I 1 I 0 I 1 = 1 σ 1 + σ 0 2σ 1 2 (SNR)1/2. (10.4.3) In relating Q to SNR, we used I 0 = 0 and set σ 0 σ 1. The latter approximation is justified for most coherent receivers whose noise is dominated by the shot noise induced by local-oscillator power and remains the same irrespective of the received signal power. Indeed, as shown in Section , the SNR of such receivers can be related to the number of photons received during each 1 bit by the simple relation SNR = 2ηN p [see Eq. ( )]. Equations (10.4.2) and (10.4.3) then provide the following expression for the BER: BER = 1 2 ηn erfc( p /4). [ASK heterodyne] (10.4.4) One can use the same method to calculate the BER in the case of ASK homodyne receivers. Equations (10.4.2) and (10.4.3) still remain applicable. However, the SNR is improved by 3 db for the homodyne case, so that SNR = 4ηN p and BER = 1 2 erfc( ηn p /2). [ASK homodyne] (10.4.5) Equations (10.4.4) and (10.4.5) can be used to calculate the receiver sensitivity at a specific BER. Similar to the direct-detection case discussed in Section 4.4, we can define the receiver sensitivity P rec as the average received power required for realizing a BER of 10 9 or less. From Eqs. (10.4.2) and (10.4.3), BER = 10 9 when Q 6or when SNR = 144 (21.6 db). For the ASK heterodyne case we can use Eq. ( ) to relate SNR to P rec if we note that P rec = P s /2 simply because signal power is zero during the 0 bits. The result is P rec = 2Q 2 hν f /η = 72hν f /η. (10.4.6) For the ASK homodyne case, P rec is smaller by a factor of 2 because of the 3-dB homodyne-detection advantage discussed in Section As an example, for a µm ASK heterodyne receiver with η = 0.8 and f = 1 GHz, the receiver sensitivity is about 12 nw and reduces to 6 nw if homodyne detection is used. The receiver sensitivity is often quoted in terms of the number of photons N p using Eqs. (10.4.4) and (10.4.5) as such a choice makes it independent of the receiver

15 492 CHAPTER 10. COHERENT LIGHTWAVE SYSTEMS bandwidth and the operating wavelength. Furthermore, η is also set to 1 so that the sensitivity corresponds to an ideal photodetector. It is easy to verify that for realizing a BER of = 10 9, N p should be 72 and 36 in the heterodyne and homodyne cases, respectively. It is important to remember that N p corresponds to the number of photons within a single 1 bit. The average number of photons per bit, N p, is reduced by a factor of 2 if we assume that 0 and 1 bits are equally likely to occur in a long bit sequence Synchronous PSK Receivers Consider first the case of heterodyne detection. The signal at the decision circuit is given by Eq. (10.3.3) or by I d = 1 2 (I p cosφ + i c ). (10.4.7) The main difference from the ASK case is that I p is constant, but the phase φ takes values 0 or π depending on whether a 1 or 0 is transmitted. In both cases, I d is a Gaussian random variable but its average value is either I p /2or I p /2, depending on the received bit. The situation is analogous to the ASK case with the difference that I 0 = I 1 in place of being zero. In fact, one can use Eq. (10.4.2) for the BER, but Q is now given by Q = I 1 I 0 2I 1 =(SNR) 1/2, (10.4.8) σ 1 + σ 0 2σ 1 where I 0 = I 1 and σ 0 = σ 1 was used. By using SNR = 2ηN p from Eq. ( ), the BER is given by BER = 1 2 erfc( ηn p ). [PSK heterodyne] (10.4.9) As before, the SNR is improved by 3 db, or by a factor of 2, in the case of PSK homodyne detection, so that BER = 1 2 erfc( 2ηN p ). [PSK homodyne] ( ) The receiver sensitivity at a BER of 10 9 can be obtained by using Q = 6 and Eq. ( ) for SNR. For the purpose of comparison, it is useful to express the receiver sensitivity in terms of the number of photons N p. It is easy to verify that N p = 18 and 9 for the cases of heterodyne and homodyne PSK detection, respectively. The average number of photons/bit, N p, equals N p for the PSK format because the same power is transmitted during 1 and 0 bits. A PSK homodyne receiver is the most sensitive receiver, requiring only 9 photons/bit. It should be emphasized that this conclusion is based on the Gaussian approximation for the receiver noise [37]. It is interesting to compare the sensitivity of coherent receivers with that of a directdetection receiver. Table 10.1 shows such a comparison. As discussed in Section 4.5.3, an ideal direct-detection receiver requires 10 photons/bit to operate at a BER of This value is only slightly inferior to the best case of a PSK homodyne receiver and considerably superior to that of heterodyne schemes. However, it is never achieved in practice because of thermal noise, dark current, and many other factors, which degrade the sensitivity to the extent that N p > 1000 is usually required. In the case of coherent receivers, N p below 100 can be realized simply because shot noise can be made dominant by increasing the local-oscillator power. The performance of coherent receivers is discussed in Section 10.6.

16 10.4. BIT-ERROR RATE 493 Table 10.1 Sensitivity of synchronous receivers Modulation Format Bit-Error Rate N p N p ASK heterodyne 1 2 erfc( ηn p /4) ASK homodyne 1 2 erfc( ηn p /2) PSK heterodyne 1 2 erfc( ηn p ) PSK homodyne 1 2 erfc( 2ηN p ) 9 9 FSK heterodyne 1 2 erfc( ηn p /2) Direct detection 1 2 exp( ηn p) Synchronous FSK Receivers Synchronous FSK receivers generally use a dual-filter scheme similar to that shown in Fig. 10.6(a) for the asynchronous case. Each filter passes only 1 or 0 bits. The scheme is equivalent to two complementary ASK heterodyne receivers operating in parallel. This feature can be used to calculate the BER of dual-filter synchronous FSK receivers. Indeed, one can use Eqs. (10.4.2) and (10.4.3) for the FSK case also. However, the SNR is improved by a factor of 2 compared with the ASK case. The improvement is due to the fact that whereas no power is received, on average, half the time for ASK receivers, the same amount of power is received all the time for FSK receivers. Hence the signal power is enhanced by a factor of 2, whereas the noise power remains the same if we assume the same receiver bandwidth in the two cases. By using SNR = 4ηN p in Eq. (10.4.3), the BER is given by BER = 1 2 erfc( ηn p /2). [FSK heterodyne] ( ) The receiver sensitivity is obtained from Eq. (10.4.6) by replacing the factor of 72 by 36. In terms of the number of photons, the sensitivity is given by N p = 36. The average number of photons/bit, N p, also equals 36, since each bit carries the same energy. A comparison of ASK and FSK heterodyne schemes in Table 10.1 shows that N p = 36 for both schemes. Therefore even though the ASK heterodyne receiver requires 72 photons within the 1 bit, the receiver sensitivity (average received power) is the same for both the ASK and FSK schemes. Figure 10.7 plots the BER as a function of N p for the ASK, PSK, and FSK formats by using Eqs. (10.4.4), (10.4.9), and ( ). The dotted curve shows the BER for the case of synchronous PSK homodyne receiver discussed in Section The dashed curves correspond to the case of asynchronous receivers discussed in the following subsections Asynchronous ASK Receivers The BER calculation for asynchronous receivers is slightly more complicated than for synchronous receivers because the noise statistics does not remain Gaussian when an

17 494 CHAPTER 10. COHERENT LIGHTWAVE SYSTEMS Figure 10.7: Bit-error-rate curves for various modulation formats. The solid and dashed lines correspond to the cases of synchronous and asynchronous demodulation, respectively. envelope detector is used (see Fig. 10.5). The reason can be understood from Eq. (10.3.4), which shows the signal received by the decision circuit. In the case of an ideal ASK heterodyne receiver without phase fluctuations, φ can be set to zero so that (subscript d is dropped for simplicity of notation) I =[(I p + i c ) 2 + i 2 s] 1/2. ( ) Even though both I p + i c and i s are Gaussian random variables, the probability density function (PDF) of I is not Gaussian. It can be calculated by using a standard technique [38] and is found to be given by [39] p(i,i p )= I σ 2 exp ( I2 + I 2 p 2σ 2 ) ( ) Ip I I 0 σ 2, ( ) where I 0 represents the modified Bessel function of the first kind. Both i c and i s are assumed to have a Gaussian PDF with zero mean and the same standard deviation σ, where σ is the RMS noise current. The PDF given by Eq. ( ) is known as the Rice distribution [39]. Note that I varies in the range 0 to, since the output of an envelope detector can have only positive values. When I p = 0, the Rice distribution reduces to the Rayleigh distribution, well known in statistical optics [38]. The BER calculation follows the analysis of Section with the only difference that the Rice distribution needs to be used in place of the Gaussian distribution. The BER is given by Eq. (4.5.2) or by BER = 1 2 [P(0/1)+P(1/0)], ( )

18 10.4. BIT-ERROR RATE 495 where ID P(0/1)= p(i,i 1 )di, 0 P(1/0)= P(I,I 0 )di. I D ( ) The notation is the same as that of Section In particular, I D is the decision level and I 1 and I 0 are values of I p for 1 and 0 bits. The noise is the same for all bits (σ 0 = σ 1 = σ) because it is dominated by the local oscillator power. The integrals in Eq. ( ) can be expressed in terms of Marcum s Q function defined as [40] The result for the BER is Q(α,β )= x exp β BER = 1 2 ( x2 + α 2 2 ) I 0 (αx)dx. ( ) [ ( I1 1 Q σ, I ) ( D I0 + Q σ σ, I )] D. ( ) σ The decision level I D is chosen such that the BER is minimum for given values of I 1, I 0, and σ. It is difficult to obtain an analytic expression of I D under general conditions. However, under typical operating conditions, I 0 0, I 1 /σ 1, and I D is well approximated by I 1 /2. The BER then becomes BER 1 2 exp( I2 1/8σ 2 )= 1 2 exp( SNR/8). ( ) When the receiver noise σ is dominated by the shot noise, the SNR is given by Eq. ( ). Using SNR = 2ηN p, we obtain the final result, BER = 1 2 exp( ηn p/4), ( ) which should be compared with Eq. (10.4.4) obtained for the case of synchronous ASK heterodyne receivers. Equation ( ) is plotted in Fig with a dashed line. It shows that the BER is larger in the asynchronous case for the same value of ηn p. However, the difference is so small that the receiver sensitivity at a BER of 10 9 is degraded by only about 0.5 db. If we assume that η = 1, Eq. ( ) shows that BER = 10 9 for N p = 80 (N p = 72 for the synchronous case). Asynchronous receivers hence provide performance comparable to that of synchronous receivers and are often used in practice because of their simpler design Asynchronous FSK Receivers Although a single-filter heterodyne receiver can be used for FSK, it has the disadvantage that one-half of the received power is rejected, resulting in an obvious 3-dB penalty. For this reason, a dual-filter FSK receiver [see Fig. 10.6(a)] is commonly employed in which 1 and 0 bits pass through separate filters. The output of two envelope detectors are subtracted, and the resulting signal is used by the decision circuit. Since the average current takes values I p and I p for 1 and 0 bits, the decision threshold is set in the middle (I D = 0). Let I and I be the currents generated in the upper and lower

19 496 CHAPTER 10. COHERENT LIGHTWAVE SYSTEMS branches of the dual filter receiver, where both of them include noise currents through Eq. ( ). Consider the case in which 1 bits are received in the upper branch. The current I is then given by Eq. ( ) and follows a Rice distribution with I p = I 1 in Eq. ( ). On the other hand, I consists only of noise and its distribution is obtained by setting I p = 0 in Eq. ( ). An error is made when I > I, as the signal is then below the decision level, resulting in [ ] P(0/1)= p(i,i 1 ) p(i,0)di di, ( ) 0 I where the inner integral provides the error probability for a fixed value of I and the outer integral sums it over all possible values of I. The probability P(1/0) can be obtained similarly. In fact, P(1/0) =P(0/1) because of the symmetric nature of a dual-filter receiver. The integral in Eq. ( ) can be evaluated analytically. By using Eq. ( ) in the inner integral with I p = 0, it is easy to verify that ) p(i,0)di = exp ( I2 I 2σ 2. ( ) By using Eqs. ( ), ( ), and ( ) with P(1/0)=P(0/1), the BER is given by ( I BER = σ 2 exp I2 + I1 2 ) ( ) ) I1 I 2σ 2 I 0 σ 2 exp ( I2 2σ 2 di, ( ) 0 where p(i,i p ) was substituted from Eq. ( ). By introducing the variable x = 2I, Eq. ( ) can be written as BER = 1 ( ) 2 exp I2 ( x 4σ 2 0 σ 2 exp x2 + I1 2/2 ) ( ) I1 x 2σ 2 I 0 σ 2 dx. ( ) 2 The integrand in Eq. ( ) is just p(x,i 1 / 2) and the integral must be 1. The BER is thus simply given by BER = 1 2 exp( I2 1 /4σ 2 )= 1 2 exp( SNR/4). ( ) By using SNR = 2ηN p from Eq. ( ), we obtain the final result BER = 1 2 exp( ηn p/2), ( ) which should be compared with Eq. ( ) obtained for the case of synchronous FSK heterodyne receivers. Figure 10.7 compares the BER in the two cases. Just as in the ASK case, the BER is larger for asynchronous demodulation. However, the difference is small, and the receiver sensitivity is degraded by only about 0.5 db compared with the synchronous case. If we assume that η = 1, N p = 40 at a BER of 10 9 (N p = 36 in the synchronous case). N p also equals 40, since the same number of photons are received during 1 and 0 bits. Similar to the synchronous case, N p is the same for both the ASK and FSK formats.

20 10.5. SENSITIVITY DEGRADATION 497 Table 10.2 Sensitivity of asynchronous receivers Modulation Format Bit-Error Rate N p N p ASK heterodyne 1 2 exp( ηn p /4) FSK heterodyne 1 2 exp( ηn p /2) DPSK heterodyne 1 2 exp( ηn p) Direct detection 1 2 exp( ηn p ) Asynchronous DPSK Receivers As mentioned in Section , asynchronous demodulation cannot be used for PSK signals. A variant of PSK, known as DPSK, can be demodulated by using an asynchronous DPSK receiver [see Fig. 10.6(b)]. The filtered current is divided into two parts, and one part is delayed by exactly one bit period. The product of two currents contains information about the phase difference between the two neighboring bits and is used by the decision current to determine the bit pattern. The BER calculation is more complicated for the DPSK case because the signal is formed by the product of two currents. The final result is, however, quite simple and is given by [11] BER = 1 2 exp( ηn p). ( ) It can be obtained from the FSK result, Eq. ( ), by using a simple argument which shows that the demodulated DPSK signal corresponds to the FSK case if we replace I 1 by 2I 1 and σ 2 by 2σ 2 [13]. Figure 10.7 shows the BER by a dashed line (the curve marked DPSK). For η = 1, a BER of 10 9 is obtained for N p = 20. Thus, a DPSK receiver is more sensitive by 3 db compared with both ASK and FSK receivers. Table 10.2 lists the BER and the receiver sensitivity for the three modulation schemes used with asynchronous demodulation. The quantum limit of a direct-detection receiver is also listed for comparison. The sensitivity of an asynchronous DPSK receiver is only 3 db away from this quantum limit Sensitivity Degradation The sensitivity analysis of the preceding section assumes ideal operating conditions for a coherent lightwave system with perfect components. Many physical mechanisms degrade the receiver sensitivity in practical coherent systems; among them are phase noise, intensity noise, polarization mismatch, and fiber dispersion. In this section we discuss the sensitivity-degradation mechanisms and the techniques used to improve the performance with a proper receiver design.

21 498 CHAPTER 10. COHERENT LIGHTWAVE SYSTEMS Phase Noise An important source of sensitivity degradation in coherent lightwave systems is the phase noise associated with the transmitter laser and the local oscillator. The reason can be understood from Eqs. (10.1.5) and (10.1.7), which show the current generated at the photodetector for homodyne and heterodyne receivers, respectively. In both cases, phase fluctuations lead to current fluctuations and degrade the SNR. Both the signal phase φ s and the local-oscillator phase φ LO should remain relatively stable to avoid the sensitivity degradation. A measure of the duration over which the laser phase remains relatively stable is provided by the coherence time. As the coherence time is inversely related to the laser linewidth ν, it is common to use the linewidth-tobit rate ratio, ν/b, to characterize the effects of phase noise on the performance of coherent lightwave systems. Since both φ s and φ LO fluctuate independently, ν is actually the sum of the linewidths ν T and ν LO associated with the transmitter and the local oscillator, respectively. The quantity ν = ν T + ν LO is often called the IF linewidth. Considerable attention has been paid to calculate the BER in the presence of phase noise and to estimate the dependence of the power penalty on the ratio ν/b [41] [55]. The tolerable value of ν/b for which the power penalty remains below 1 db depends on the modulation format as well as on the demodulation technique. In general, the linewidth requirements are most stringent for homodyne receivers. Although the tolerable linewidth depends to some extent on the design of phase-locked loop, typically ν/b should be < to realize a power penalty of less than 1 db [43]. The requirement becomes ν/b < if the penalty is to be kept below 0.5 db [44]. The linewidth requirements are relaxed considerably for heterodyne receivers, especially in the case of asynchronous demodulation with the ASK or FSK modulation format. For synchronous heterodyne receivers ν/b < is required [46]. In contrast, ν/b can exceed 0.1 for asynchronous ASK and FSK receivers [49] [52]. The reason is related to the fact that such receivers use an envelope detector (see Fig. 10.5) that throws away the phase information. The effect of phase fluctuations is mainly to broaden the signal bandwidth. The signal can be recovered by increasing the bandwidth of the bandpass filter (BPF). In principle, any linewidth can be tolerated if the BPF bandwidth is suitably increased. However, a penalty must be paid since receiver noise increases with an increase in the BPF bandwidth. Figure 10.8 shows how the receiver sensitivity (expressed in average number of photons/bit, N p ) degrades with ν/b for the ASK and FSK formats. The BER calculation is rather cumbersome and requires numerical simulations [51]. Approximate methods have been developed to provide the analytic results accurate to within 1 db [52]. The DPSK format requires narrower linewidths compared with the ASK and FSK formats when asynchronous demodulation based on the delay scheme [see Fig. 10.6(b)] is used. The reason is that information is contained in the phase difference between the two neighboring bits, and the phase should remain stable at least over the duration of two bits. Theoretical estimates show that generally ν/b should be less than 1% to operate with a < 1 db power penalty [43]. For a 1-Gb/s bit rate, the required linewidth is 1 MHz but becomes < 1 MHz at lower bit rates. The design of coherent lightwave systems requires semiconductor lasers that oper-

Table 10.2 Sensitivity of asynchronous receivers. Modulation Format Bit-Error Rate N p. 1 2 FSK heterodyne. ASK heterodyne. exp( ηn p /2) 40 40

Table 10.2 Sensitivity of asynchronous receivers. Modulation Format Bit-Error Rate N p. 1 2 FSK heterodyne. ASK heterodyne. exp( ηn p /2) 40 40 10.5. SENSITIVITY DEGRADATION 497 Table 10.2 Sensitivity of asynchronous receivers Modulation Format Bit-Error Rate N p N p ASK heterodyne 1 2 exp( ηn p /4) 80 40 FSK heterodyne 1 2 exp( ηn p /2) 40 40

More information

Optical Coherent Receiver Analysis

Optical Coherent Receiver Analysis Optical Coherent Receiver Analysis 7 Capella Court Nepean, ON, Canada K2E 7X1 +1 (613) 224-4700 www.optiwave.com 2009 Optiwave Systems, Inc. Introduction (1) Coherent receiver analysis Optical coherent

More information

2. Digital Optical Systems based on Coherent and Direct Detection

2. Digital Optical Systems based on Coherent and Direct Detection 1/ 2. Digital Optical Systems based on Coherent and Direct Detection Optical Communication Systems and Networks 2/ 12 BIBLIOGRAPHY Fiber-Optic Communications Systems Govind P. Agrawal, Chapter 10, pp.

More information

Opto-electronic Receivers

Opto-electronic Receivers Purpose of a Receiver The receiver fulfils the function of optoelectronic conversion of an input optical signal into an output electrical signal (data stream). The purpose is to recover the data transmitted

More information

Lecture 8 Fiber Optical Communication Lecture 8, Slide 1

Lecture 8 Fiber Optical Communication Lecture 8, Slide 1 Lecture 8 Bit error rate The Q value Receiver sensitivity Sensitivity degradation Extinction ratio RIN Timing jitter Chirp Forward error correction Fiber Optical Communication Lecture 8, Slide Bit error

More information

FIBER OPTICS. Prof. R.K. Shevgaonkar. Department of Electrical Engineering. Indian Institute of Technology, Bombay. Lecture: 22.

FIBER OPTICS. Prof. R.K. Shevgaonkar. Department of Electrical Engineering. Indian Institute of Technology, Bombay. Lecture: 22. FIBER OPTICS Prof. R.K. Shevgaonkar Department of Electrical Engineering Indian Institute of Technology, Bombay Lecture: 22 Optical Receivers Fiber Optics, Prof. R.K. Shevgaonkar, Dept. of Electrical Engineering,

More information

Lecture 7 Fiber Optical Communication Lecture 7, Slide 1

Lecture 7 Fiber Optical Communication Lecture 7, Slide 1 Dispersion management Lecture 7 Dispersion compensating fibers (DCF) Fiber Bragg gratings (FBG) Dispersion-equalizing filters Optical phase conjugation (OPC) Electronic dispersion compensation (EDC) Fiber

More information

Fiber-Optic Communication Systems

Fiber-Optic Communication Systems Fiber-Optic Communication Systems Second Edition GOVIND P. AGRAWAL The Institute of Optics University of Rochester Rochester, NY A WILEY-iNTERSCIENCE PUBLICATION JOHN WILEY & SONS, INC. NEW YORK / CHICHESTER

More information

Module 12 : System Degradation and Power Penalty

Module 12 : System Degradation and Power Penalty Module 12 : System Degradation and Power Penalty Lecture : System Degradation and Power Penalty Objectives In this lecture you will learn the following Degradation during Propagation Modal Noise Dispersion

More information

B.Tech II Year II Semester (R13) Supplementary Examinations May/June 2017 ANALOG COMMUNICATION SYSTEMS (Electronics and Communication Engineering)

B.Tech II Year II Semester (R13) Supplementary Examinations May/June 2017 ANALOG COMMUNICATION SYSTEMS (Electronics and Communication Engineering) Code: 13A04404 R13 B.Tech II Year II Semester (R13) Supplementary Examinations May/June 2017 ANALOG COMMUNICATION SYSTEMS (Electronics and Communication Engineering) Time: 3 hours Max. Marks: 70 PART A

More information

Module 10 : Receiver Noise and Bit Error Ratio

Module 10 : Receiver Noise and Bit Error Ratio Module 10 : Receiver Noise and Bit Error Ratio Lecture : Receiver Noise and Bit Error Ratio Objectives In this lecture you will learn the following Receiver Noise and Bit Error Ratio Shot Noise Thermal

More information

A NOVEL SCHEME FOR OPTICAL MILLIMETER WAVE GENERATION USING MZM

A NOVEL SCHEME FOR OPTICAL MILLIMETER WAVE GENERATION USING MZM A NOVEL SCHEME FOR OPTICAL MILLIMETER WAVE GENERATION USING MZM Poomari S. and Arvind Chakrapani Department of Electronics and Communication Engineering, Karpagam College of Engineering, Coimbatore, Tamil

More information

Lecture 2 Fiber Optical Communication Lecture 2, Slide 1

Lecture 2 Fiber Optical Communication Lecture 2, Slide 1 Lecture 2 General concepts Digital modulation in general Optical modulation Direct modulation External modulation Modulation formats Differential detection Coherent detection Fiber Optical Communication

More information

π code 0 Changchun,130000,China Key Laboratory of National Defense.Changchun,130000,China Keywords:DPSK; CSRZ; atmospheric channel

π code 0 Changchun,130000,China Key Laboratory of National Defense.Changchun,130000,China Keywords:DPSK; CSRZ; atmospheric channel 4th International Conference on Computer, Mechatronics, Control and Electronic Engineering (ICCMCEE 2015) Differential phase shift keying in the research on the effects of type pattern of space optical

More information

Local Oscillator Phase Noise and its effect on Receiver Performance C. John Grebenkemper

Local Oscillator Phase Noise and its effect on Receiver Performance C. John Grebenkemper Watkins-Johnson Company Tech-notes Copyright 1981 Watkins-Johnson Company Vol. 8 No. 6 November/December 1981 Local Oscillator Phase Noise and its effect on Receiver Performance C. John Grebenkemper All

More information

Lecture 6 Fiber Optical Communication Lecture 6, Slide 1

Lecture 6 Fiber Optical Communication Lecture 6, Slide 1 Lecture 6 Optical transmitters Photon processes in light matter interaction Lasers Lasing conditions The rate equations CW operation Modulation response Noise Light emitting diodes (LED) Power Modulation

More information

SHF Communication Technologies AG

SHF Communication Technologies AG SHF Communication Technologies AG Wilhelm-von-Siemens-Str. 23 Aufgang D 12277 Berlin Marienfelde Germany Phone ++49 30 / 772 05 10 Fax ++49 30 / 753 10 78 E-Mail: sales@shf.biz Web: http://www.shf.biz

More information

Optical Complex Spectrum Analyzer (OCSA)

Optical Complex Spectrum Analyzer (OCSA) Optical Complex Spectrum Analyzer (OCSA) First version 24/11/2005 Last Update 05/06/2013 Distribution in the UK & Ireland Characterisation, Measurement & Analysis Lambda Photometrics Limited Lambda House

More information

FIBER OPTICS. Prof. R.K. Shevgaonkar. Department of Electrical Engineering. Indian Institute of Technology, Bombay. Lecture: 24. Optical Receivers-

FIBER OPTICS. Prof. R.K. Shevgaonkar. Department of Electrical Engineering. Indian Institute of Technology, Bombay. Lecture: 24. Optical Receivers- FIBER OPTICS Prof. R.K. Shevgaonkar Department of Electrical Engineering Indian Institute of Technology, Bombay Lecture: 24 Optical Receivers- Receiver Sensitivity Degradation Fiber Optics, Prof. R.K.

More information

Narrow- and wideband channels

Narrow- and wideband channels RADIO SYSTEMS ETIN15 Lecture no: 3 Narrow- and wideband channels Ove Edfors, Department of Electrical and Information technology Ove.Edfors@eit.lth.se 2012-03-19 Ove Edfors - ETIN15 1 Contents Short review

More information

Module 16 : Integrated Optics I

Module 16 : Integrated Optics I Module 16 : Integrated Optics I Lecture : Integrated Optics I Objectives In this lecture you will learn the following Introduction Electro-Optic Effect Optical Phase Modulator Optical Amplitude Modulator

More information

EXAMINATION FOR THE DEGREE OF B.E. and M.E. Semester

EXAMINATION FOR THE DEGREE OF B.E. and M.E. Semester EXAMINATION FOR THE DEGREE OF B.E. and M.E. Semester 2 2009 101908 OPTICAL COMMUNICATION ENGINEERING (Elec Eng 4041) 105302 SPECIAL STUDIES IN MARINE ENGINEERING (Elec Eng 7072) Official Reading Time:

More information

Optical Fibers p. 1 Basic Concepts p. 1 Step-Index Fibers p. 2 Graded-Index Fibers p. 4 Design and Fabrication p. 6 Silica Fibers p.

Optical Fibers p. 1 Basic Concepts p. 1 Step-Index Fibers p. 2 Graded-Index Fibers p. 4 Design and Fabrication p. 6 Silica Fibers p. Preface p. xiii Optical Fibers p. 1 Basic Concepts p. 1 Step-Index Fibers p. 2 Graded-Index Fibers p. 4 Design and Fabrication p. 6 Silica Fibers p. 6 Plastic Optical Fibers p. 9 Microstructure Optical

More information

An improved optical costas loop PSK receiver: Simulation analysis

An improved optical costas loop PSK receiver: Simulation analysis Journal of Scientific HELALUDDIN: & Industrial Research AN IMPROVED OPTICAL COSTAS LOOP PSK RECEIVER: SIMULATION ANALYSIS 203 Vol. 67, March 2008, pp. 203-208 An improved optical costas loop PSK receiver:

More information

The secondary MZM used to modulate the quadrature phase carrier produces a phase shifted version:

The secondary MZM used to modulate the quadrature phase carrier produces a phase shifted version: QAM Receiver 1 OBJECTIVE Build a coherent receiver based on the 90 degree optical hybrid and further investigate the QAM format. 2 PRE-LAB In the Modulation Formats QAM Transmitters laboratory, a method

More information

EENG473 Mobile Communications Module 3 : Week # (12) Mobile Radio Propagation: Small-Scale Path Loss

EENG473 Mobile Communications Module 3 : Week # (12) Mobile Radio Propagation: Small-Scale Path Loss EENG473 Mobile Communications Module 3 : Week # (12) Mobile Radio Propagation: Small-Scale Path Loss Introduction Small-scale fading is used to describe the rapid fluctuation of the amplitude of a radio

More information

Code No: R Set No. 1

Code No: R Set No. 1 Code No: R05220405 Set No. 1 II B.Tech II Semester Regular Examinations, Apr/May 2007 ANALOG COMMUNICATIONS ( Common to Electronics & Communication Engineering and Electronics & Telematics) Time: 3 hours

More information

ECEN689: Special Topics in Optical Interconnects Circuits and Systems Spring 2016

ECEN689: Special Topics in Optical Interconnects Circuits and Systems Spring 2016 ECEN689: Special Topics in Optical Interconnects Circuits and Systems Spring 016 Lecture 7: Transmitter Analysis Sam Palermo Analog & Mixed-Signal Center Texas A&M University Optical Modulation Techniques

More information

Chapter 4. Part 2(a) Digital Modulation Techniques

Chapter 4. Part 2(a) Digital Modulation Techniques Chapter 4 Part 2(a) Digital Modulation Techniques Overview Digital Modulation techniques Bandpass data transmission Amplitude Shift Keying (ASK) Phase Shift Keying (PSK) Frequency Shift Keying (FSK) Quadrature

More information

Amplitude Frequency Phase

Amplitude Frequency Phase Chapter 4 (part 2) Digital Modulation Techniques Chapter 4 (part 2) Overview Digital Modulation techniques (part 2) Bandpass data transmission Amplitude Shift Keying (ASK) Phase Shift Keying (PSK) Frequency

More information

Channel. Muhammad Ali Jinnah University, Islamabad Campus, Pakistan. Multi-Path Fading. Dr. Noor M Khan EE, MAJU

Channel. Muhammad Ali Jinnah University, Islamabad Campus, Pakistan. Multi-Path Fading. Dr. Noor M Khan EE, MAJU Instructor: Prof. Dr. Noor M. Khan Department of Electronic Engineering, Muhammad Ali Jinnah University, Islamabad Campus, Islamabad, PAKISTAN Ph: +9 (51) 111-878787, Ext. 19 (Office), 186 (Lab) Fax: +9

More information

Optical phase-locked loop for coherent transmission over 500 km using heterodyne detection with fiber lasers

Optical phase-locked loop for coherent transmission over 500 km using heterodyne detection with fiber lasers Optical phase-locked loop for coherent transmission over 500 km using heterodyne detection with fiber lasers Keisuke Kasai a), Jumpei Hongo, Masato Yoshida, and Masataka Nakazawa Research Institute of

More information

Advanced Lightwave Systems

Advanced Lightwave Systems Chapter 10 Advanced Lightwave Systems Lightwave systems discussed so far are based on a simple digital modulation scheme in which an electrical binary bit stream modulates the intensity of an optical carrier

More information

EE 460L University of Nevada, Las Vegas ECE Department

EE 460L University of Nevada, Las Vegas ECE Department EE 460L PREPARATION 1- ASK Amplitude shift keying - ASK - in the context of digital communications is a modulation process which imparts to a sinusoid two or more discrete amplitude levels. These are related

More information

Digital Modulation Schemes

Digital Modulation Schemes Digital Modulation Schemes 1. In binary data transmission DPSK is preferred to PSK because (a) a coherent carrier is not required to be generated at the receiver (b) for a given energy per bit, the probability

More information

EE 400L Communications. Laboratory Exercise #7 Digital Modulation

EE 400L Communications. Laboratory Exercise #7 Digital Modulation EE 400L Communications Laboratory Exercise #7 Digital Modulation Department of Electrical and Computer Engineering University of Nevada, at Las Vegas PREPARATION 1- ASK Amplitude shift keying - ASK - in

More information

Thus there are three basic modulation techniques: 1) AMPLITUDE SHIFT KEYING 2) FREQUENCY SHIFT KEYING 3) PHASE SHIFT KEYING

Thus there are three basic modulation techniques: 1) AMPLITUDE SHIFT KEYING 2) FREQUENCY SHIFT KEYING 3) PHASE SHIFT KEYING CHAPTER 5 Syllabus 1) Digital modulation formats 2) Coherent binary modulation techniques 3) Coherent Quadrature modulation techniques 4) Non coherent binary modulation techniques. Digital modulation formats:

More information

Problem Sheet 1 Probability, random processes, and noise

Problem Sheet 1 Probability, random processes, and noise Problem Sheet 1 Probability, random processes, and noise 1. If F X (x) is the distribution function of a random variable X and x 1 x 2, show that F X (x 1 ) F X (x 2 ). 2. Use the definition of the cumulative

More information

Performance Limitations of WDM Optical Transmission System Due to Cross-Phase Modulation in Presence of Chromatic Dispersion

Performance Limitations of WDM Optical Transmission System Due to Cross-Phase Modulation in Presence of Chromatic Dispersion Performance Limitations of WDM Optical Transmission System Due to Cross-Phase Modulation in Presence of Chromatic Dispersion M. A. Khayer Azad and M. S. Islam Institute of Information and Communication

More information

Lecture 5 Fiber Optical Communication Lecture 5, Slide 1

Lecture 5 Fiber Optical Communication Lecture 5, Slide 1 Lecture 5 Bit error rate The Q value Receiver sensitivity Sensitivity degradation Extinction ratio RIN Timing jitter Chirp Forward error correction Fiber Optical Communication Lecture 5, Slide 1 Bit error

More information

ECE5713 : Advanced Digital Communications

ECE5713 : Advanced Digital Communications ECE5713 : Advanced Digital Communications Bandpass Modulation MPSK MASK, OOK MFSK 04-May-15 Advanced Digital Communications, Spring-2015, Week-8 1 In-phase and Quadrature (I&Q) Representation Any bandpass

More information

Next-Generation Optical Fiber Network Communication

Next-Generation Optical Fiber Network Communication Next-Generation Optical Fiber Network Communication Naveen Panwar; Pankaj Kumar & manupanwar46@gmail.com & chandra.pankaj30@gmail.com ABSTRACT: In all over the world, much higher order off modulation formats

More information

TSEK02: Radio Electronics Lecture 8: RX Nonlinearity Issues, Demodulation. Ted Johansson, EKS, ISY

TSEK02: Radio Electronics Lecture 8: RX Nonlinearity Issues, Demodulation. Ted Johansson, EKS, ISY TSEK02: Radio Electronics Lecture 8: RX Nonlinearity Issues, Demodulation Ted Johansson, EKS, ISY RX Nonlinearity Issues: 2.2, 2.4 Demodulation: not in the book 2 RX nonlinearities System Nonlinearity

More information

Phase Noise Compensation for Coherent Orthogonal Frequency Division Multiplexing in Optical Fiber Communications Systems

Phase Noise Compensation for Coherent Orthogonal Frequency Division Multiplexing in Optical Fiber Communications Systems Jassim K. Hmood Department of Laser and Optoelectronic Engineering, University of Technology, Baghdad, Iraq Phase Noise Compensation for Coherent Orthogonal Frequency Division Multiplexing in Optical Fiber

More information

All-Optical Signal Processing and Optical Regeneration

All-Optical Signal Processing and Optical Regeneration 1/36 All-Optical Signal Processing and Optical Regeneration Govind P. Agrawal Institute of Optics University of Rochester Rochester, NY 14627 c 2007 G. P. Agrawal Outline Introduction Major Nonlinear Effects

More information

Lecture 4 Fiber Optical Communication Lecture 4, Slide 1

Lecture 4 Fiber Optical Communication Lecture 4, Slide 1 Lecture 4 Optical transmitters Photon processes in light matter interaction Lasers Lasing conditions The rate equations CW operation Modulation response Noise Light emitting diodes (LED) Power Modulation

More information

Advanced Optical Communications Prof. R. K. Shevgaonkar Department of Electrical Engineering Indian Institute of Technology, Bombay

Advanced Optical Communications Prof. R. K. Shevgaonkar Department of Electrical Engineering Indian Institute of Technology, Bombay Advanced Optical Communications Prof. R. K. Shevgaonkar Department of Electrical Engineering Indian Institute of Technology, Bombay Lecture No. # 27 EDFA In the last lecture, we talked about wavelength

More information

Multi-Path Fading Channel

Multi-Path Fading Channel Instructor: Prof. Dr. Noor M. Khan Department of Electronic Engineering, Muhammad Ali Jinnah University, Islamabad Campus, Islamabad, PAKISTAN Ph: +9 (51) 111-878787, Ext. 19 (Office), 186 (Lab) Fax: +9

More information

Frequency Modulation

Frequency Modulation Frequency Modulation transferred to the microwave carrier by means of FM. Instead of being done in one step, this modulation usually takes place at an intermediate frequency. signal is then frequency multiplied

More information

FIBER OPTICS. Prof. R.K. Shevgaonkar. Department of Electrical Engineering. Indian Institute of Technology, Bombay. Lecture: 20

FIBER OPTICS. Prof. R.K. Shevgaonkar. Department of Electrical Engineering. Indian Institute of Technology, Bombay. Lecture: 20 FIBER OPTICS Prof. R.K. Shevgaonkar Department of Electrical Engineering Indian Institute of Technology, Bombay Lecture: 20 Photo-Detectors and Detector Noise Fiber Optics, Prof. R.K. Shevgaonkar, Dept.

More information

DIGITAL COMMUNICATIONS SYSTEMS. MSc in Electronic Technologies and Communications

DIGITAL COMMUNICATIONS SYSTEMS. MSc in Electronic Technologies and Communications DIGITAL COMMUNICATIONS SYSTEMS MSc in Electronic Technologies and Communications Bandpass binary signalling The common techniques of bandpass binary signalling are: - On-off keying (OOK), also known as

More information

CALIFORNIA STATE UNIVERSITY, NORTHRIDGE FADING CHANNEL CHARACTERIZATION AND MODELING

CALIFORNIA STATE UNIVERSITY, NORTHRIDGE FADING CHANNEL CHARACTERIZATION AND MODELING CALIFORNIA STATE UNIVERSITY, NORTHRIDGE FADING CHANNEL CHARACTERIZATION AND MODELING A graduate project submitted in partial fulfillment of the requirements For the degree of Master of Science in Electrical

More information

Mobile Radio Propagation: Small-Scale Fading and Multi-path

Mobile Radio Propagation: Small-Scale Fading and Multi-path Mobile Radio Propagation: Small-Scale Fading and Multi-path 1 EE/TE 4365, UT Dallas 2 Small-scale Fading Small-scale fading, or simply fading describes the rapid fluctuation of the amplitude of a radio

More information

Lightwave Technique of mm-wave Generation for Broadband Mobile Communication

Lightwave Technique of mm-wave Generation for Broadband Mobile Communication PIERS ONLINE, VOL. 3, NO. 7, 2007 1071 Lightwave Technique of mm-wave Generation for Broadband Mobile Communication B. N. Biswas 1, A. Banerjee 1, A. Mukherjee 1, and S. Kar 2 1 Academy of Technology,

More information

Signals and Systems Lecture 9 Communication Systems Frequency-Division Multiplexing and Frequency Modulation (FM)

Signals and Systems Lecture 9 Communication Systems Frequency-Division Multiplexing and Frequency Modulation (FM) Signals and Systems Lecture 9 Communication Systems Frequency-Division Multiplexing and Frequency Modulation (FM) April 11, 2008 Today s Topics 1. Frequency-division multiplexing 2. Frequency modulation

More information

QAM Transmitter 1 OBJECTIVE 2 PRE-LAB. Investigate the method for measuring the BER accurately and the distortions present in coherent modulators.

QAM Transmitter 1 OBJECTIVE 2 PRE-LAB. Investigate the method for measuring the BER accurately and the distortions present in coherent modulators. QAM Transmitter 1 OBJECTIVE Investigate the method for measuring the BER accurately and the distortions present in coherent modulators. 2 PRE-LAB The goal of optical communication systems is to transmit

More information

Performance Analysis Of Hybrid Optical OFDM System With High Order Dispersion Compensation

Performance Analysis Of Hybrid Optical OFDM System With High Order Dispersion Compensation Performance Analysis Of Hybrid Optical OFDM System With High Order Dispersion Compensation Manpreet Singh Student, University College of Engineering, Punjabi University, Patiala, India. Abstract Orthogonal

More information

Non-coherent pulse compression - concept and waveforms Nadav Levanon and Uri Peer Tel Aviv University

Non-coherent pulse compression - concept and waveforms Nadav Levanon and Uri Peer Tel Aviv University Non-coherent pulse compression - concept and waveforms Nadav Levanon and Uri Peer Tel Aviv University nadav@eng.tau.ac.il Abstract - Non-coherent pulse compression (NCPC) was suggested recently []. It

More information

PULSE CODE MODULATION TELEMETRY Properties of Various Binary Modulation Types

PULSE CODE MODULATION TELEMETRY Properties of Various Binary Modulation Types PULSE CODE MODULATION TELEMETRY Properties of Various Binary Modulation Types Eugene L. Law Telemetry Engineer Code 1171 Pacific Missile Test Center Point Mugu, CA 93042 ABSTRACT This paper discusses the

More information

MICROWAVE photonics is an interdisciplinary area

MICROWAVE photonics is an interdisciplinary area 314 JOURNAL OF LIGHTWAVE TECHNOLOGY, VOL. 27, NO. 3, FEBRUARY 1, 2009 Microwave Photonics Jianping Yao, Senior Member, IEEE, Member, OSA (Invited Tutorial) Abstract Broadband and low loss capability of

More information

EE3723 : Digital Communications

EE3723 : Digital Communications EE3723 : Digital Communications Week 8-9: Bandpass Modulation MPSK MASK, OOK MFSK 04-May-15 Muhammad Ali Jinnah University, Islamabad - Digital Communications - EE3723 1 In-phase and Quadrature (I&Q) Representation

More information

Understanding the performance of atmospheric free-space laser communications systems using coherent detection

Understanding the performance of atmospheric free-space laser communications systems using coherent detection !"#$%&'()*+&, Understanding the performance of atmospheric free-space laser communications systems using coherent detection Aniceto Belmonte Technical University of Catalonia, Department of Signal Theory

More information

Coherent Receivers Principles Downconversion

Coherent Receivers Principles Downconversion Coherent Receivers Principles Downconversion Heterodyne receivers mix signals of different frequency; if two such signals are added together, they beat against each other. The resulting signal contains

More information

Chapter 3 Experimental study and optimization of OPLLs

Chapter 3 Experimental study and optimization of OPLLs 27 Chapter 3 Experimental study and optimization of OPLLs In Chapter 2 I have presented the theory of OPLL and identified critical issues for OPLLs using SCLs. In this chapter I will present the detailed

More information

Phase Modulator for Higher Order Dispersion Compensation in Optical OFDM System

Phase Modulator for Higher Order Dispersion Compensation in Optical OFDM System Phase Modulator for Higher Order Dispersion Compensation in Optical OFDM System Manpreet Singh 1, Karamjit Kaur 2 Student, University College of Engineering, Punjabi University, Patiala, India 1. Assistant

More information

TSEK02: Radio Electronics Lecture 8: RX Nonlinearity Issues, Demodulation. Ted Johansson, EKS, ISY

TSEK02: Radio Electronics Lecture 8: RX Nonlinearity Issues, Demodulation. Ted Johansson, EKS, ISY TSEK02: Radio Electronics Lecture 8: RX Nonlinearity Issues, Demodulation Ted Johansson, EKS, ISY 2 RX Nonlinearity Issues, Demodulation RX nonlinearities (parts of 2.2) System Nonlinearity Sensitivity

More information

EXPERIMENT WISE VIVA QUESTIONS

EXPERIMENT WISE VIVA QUESTIONS EXPERIMENT WISE VIVA QUESTIONS Pulse Code Modulation: 1. Draw the block diagram of basic digital communication system. How it is different from analog communication system. 2. What are the advantages of

More information

Narrow- and wideband channels

Narrow- and wideband channels RADIO SYSTEMS ETIN15 Lecture no: 3 Narrow- and wideband channels Ove Edfors, Department of Electrical and Information technology Ove.Edfors@eit.lth.se 27 March 2017 1 Contents Short review NARROW-BAND

More information

DC VI R 1 31D92t. e~~~ nr 71. !llll!llllllli1111ll QStanford

DC VI R 1 31D92t. e~~~ nr 71. !llll!llllllli1111ll QStanford L. G. Kazovsky, J. C. Fan: "Coherent analog FM-SCM video.. 10 Coherent analog FM-SCM video transmission using S -direct frequency modulation of semiconductor lasers N L. G. Kazovsky, J. C. Fan Department

More information

IST IP NOBEL "Next generation Optical network for Broadband European Leadership"

IST IP NOBEL Next generation Optical network for Broadband European Leadership DBR Tunable Lasers A variation of the DFB laser is the distributed Bragg reflector (DBR) laser. It operates in a similar manner except that the grating, instead of being etched into the gain medium, is

More information

Revision of Previous Six Lectures

Revision of Previous Six Lectures Revision of Previous Six Lectures Previous six lectures have concentrated on Modem, under ideal AWGN or flat fading channel condition Important issues discussed need to be revised, and they are summarised

More information

Lecture 9 External Modulators and Detectors

Lecture 9 External Modulators and Detectors Optical Fibres and Telecommunications Lecture 9 External Modulators and Detectors Introduction Where are we? A look at some real laser diodes. External modulators Mach-Zender Electro-absorption modulators

More information

Outline. Communications Engineering 1

Outline. Communications Engineering 1 Outline Introduction Signal, random variable, random process and spectra Analog modulation Analog to digital conversion Digital transmission through baseband channels Signal space representation Optimal

More information

RF/IF Terminology and Specs

RF/IF Terminology and Specs RF/IF Terminology and Specs Contributors: Brad Brannon John Greichen Leo McHugh Eamon Nash Eberhard Brunner 1 Terminology LNA - Low-Noise Amplifier. A specialized amplifier to boost the very small received

More information

Efficiency of complex modulation methods in coherent free-space optical links

Efficiency of complex modulation methods in coherent free-space optical links Efficiency of complex modulation methods in coherent free-space optical links Aniceto Belmonte 1,* and Joseph M. Kahn 1 Technical University of Catalonia, Department of Signal Theory and Communications,

More information

Timing Noise Measurement of High-Repetition-Rate Optical Pulses

Timing Noise Measurement of High-Repetition-Rate Optical Pulses 564 Timing Noise Measurement of High-Repetition-Rate Optical Pulses Hidemi Tsuchida National Institute of Advanced Industrial Science and Technology 1-1-1 Umezono, Tsukuba, 305-8568 JAPAN Tel: 81-29-861-5342;

More information

EE4512 Analog and Digital Communications Chapter 6. Chapter 6 Analog Modulation and Demodulation

EE4512 Analog and Digital Communications Chapter 6. Chapter 6 Analog Modulation and Demodulation Chapter 6 Analog Modulation and Demodulation Chapter 6 Analog Modulation and Demodulation Amplitude Modulation Pages 306-309 309 The analytical signal for double sideband, large carrier amplitude modulation

More information

CHAPTER 4 RESULTS. 4.1 Introduction

CHAPTER 4 RESULTS. 4.1 Introduction CHAPTER 4 RESULTS 4.1 Introduction In this chapter focus are given more on WDM system. The results which are obtained mainly from the simulation work are presented. In simulation analysis, the study will

More information

Universitas Sumatera Utara

Universitas Sumatera Utara Amplitude Shift Keying & Frequency Shift Keying Aim: To generate and demodulate an amplitude shift keyed (ASK) signal and a binary FSK signal. Intro to Generation of ASK Amplitude shift keying - ASK -

More information

Optical Communication Systems (OPT428)

Optical Communication Systems (OPT428) 1/549 Optical Communication Systems (OPT428) Govind P. Agrawal Institute of Optics University of Rochester Rochester, NY 14627 c 2007 G. P. Agrawal Course Outline Introduction Optical Signal Generation

More information

ECE 476/ECE 501C/CS Wireless Communication Systems Winter Lecture 6: Fading

ECE 476/ECE 501C/CS Wireless Communication Systems Winter Lecture 6: Fading ECE 476/ECE 501C/CS 513 - Wireless Communication Systems Winter 2004 Lecture 6: Fading Last lecture: Large scale propagation properties of wireless systems - slowly varying properties that depend primarily

More information

S Optical Networks Course Lecture 3: Modulation and Demodulation

S Optical Networks Course Lecture 3: Modulation and Demodulation S-72.3340 Optical Networks Course Lecture 3: Modulation and Demodulation Edward Mutafungwa Communications Laboratory, Helsinki University of Technology, P. O. Box 2300, FIN-02015 TKK, Finland Tel: +358

More information

BER Analysis for Synchronous All-Optical CDMA LANs with Modified Prime Codes

BER Analysis for Synchronous All-Optical CDMA LANs with Modified Prime Codes BER Analysis for Synchronous All-Optical CDMA LANs with Modified Prime Codes Pham Manh Lam Faculty of Science and Technology, Assumption University Bangkok, Thailand Abstract The analysis of the BER performance

More information

ECE 476/ECE 501C/CS Wireless Communication Systems Winter Lecture 6: Fading

ECE 476/ECE 501C/CS Wireless Communication Systems Winter Lecture 6: Fading ECE 476/ECE 501C/CS 513 - Wireless Communication Systems Winter 2005 Lecture 6: Fading Last lecture: Large scale propagation properties of wireless systems - slowly varying properties that depend primarily

More information

Radio Receiver Architectures and Analysis

Radio Receiver Architectures and Analysis Radio Receiver Architectures and Analysis Robert Wilson December 6, 01 Abstract This article discusses some common receiver architectures and analyzes some of the impairments that apply to each. 1 Contents

More information

IIIIIii tn _. Subcarrier-Multiplexed Coherent Optical Video Transmission Using Direct Frequency Modulation of Semiconductor Lasers

IIIIIii tn _. Subcarrier-Multiplexed Coherent Optical Video Transmission Using Direct Frequency Modulation of Semiconductor Lasers J. c. Fan and L. G. Kazovsky: "Subcarrier-Multiplexed Coherent Optical Video..." 10 -_ tn _ Subcarrier-Multiplexed Coherent Optical Video Transmission Using Direct Frequency Modulation of Semiconductor

More information

UNIVERSITY OF SOUTHAMPTON

UNIVERSITY OF SOUTHAMPTON UNIVERSITY OF SOUTHAMPTON ELEC6014W1 SEMESTER II EXAMINATIONS 2007/08 RADIO COMMUNICATION NETWORKS AND SYSTEMS Duration: 120 mins Answer THREE questions out of FIVE. University approved calculators may

More information

Lecture 9: Spread Spectrum Modulation Techniques

Lecture 9: Spread Spectrum Modulation Techniques Lecture 9: Spread Spectrum Modulation Techniques Spread spectrum (SS) modulation techniques employ a transmission bandwidth which is several orders of magnitude greater than the minimum required bandwidth

More information

레이저의주파수안정화방법및그응용 박상언 ( 한국표준과학연구원, 길이시간센터 )

레이저의주파수안정화방법및그응용 박상언 ( 한국표준과학연구원, 길이시간센터 ) 레이저의주파수안정화방법및그응용 박상언 ( 한국표준과학연구원, 길이시간센터 ) Contents Frequency references Frequency locking methods Basic principle of loop filter Example of lock box circuits Quantifying frequency stability Applications

More information

Temporal phase mask encrypted optical steganography carried by amplified spontaneous emission noise

Temporal phase mask encrypted optical steganography carried by amplified spontaneous emission noise Temporal phase mask encrypted optical steganography carried by amplified spontaneous emission noise Ben Wu, * Zhenxing Wang, Bhavin J. Shastri, Matthew P. Chang, Nicholas A. Frost, and Paul R. Prucnal

More information

Downloaded from 1

Downloaded from  1 VII SEMESTER FINAL EXAMINATION-2004 Attempt ALL questions. Q. [1] How does Digital communication System differ from Analog systems? Draw functional block diagram of DCS and explain the significance of

More information

Revision of Previous Six Lectures

Revision of Previous Six Lectures Revision of Previous Six Lectures Previous six lectures have concentrated on Modem, under ideal AWGN or flat fading channel condition multiplexing multiple access CODEC MODEM Wireless Channel Important

More information

Turbo-coding of Coherence Multiplexed Optical PPM CDMA System With Balanced Detection

Turbo-coding of Coherence Multiplexed Optical PPM CDMA System With Balanced Detection American Journal of Applied Sciences 4 (5): 64-68, 007 ISSN 1546-939 007 Science Publications Turbo-coding of Coherence Multiplexed Optical PPM CDMA System With Balanced Detection K. Chitra and V.C. Ravichandran

More information

EXPERIMENT 2: Frequency Shift Keying (FSK)

EXPERIMENT 2: Frequency Shift Keying (FSK) EXPERIMENT 2: Frequency Shift Keying (FSK) 1) OBJECTIVE Generation and demodulation of a frequency shift keyed (FSK) signal 2) PRELIMINARY DISCUSSION In FSK, the frequency of a carrier signal is modified

More information

EC2252: COMMUNICATION THEORY SEM / YEAR: II year DEPARTMENT OF ELECTRONICS AND COMMUNICATION ENGINEERING

EC2252: COMMUNICATION THEORY SEM / YEAR: II year DEPARTMENT OF ELECTRONICS AND COMMUNICATION ENGINEERING EC2252: COMMUNICATION THEORY SEM / YEAR: II year DEPARTMENT OF ELECTRONICS AND COMMUNICATION ENGINEERING QUESTION BANK SUBJECT CODE : EC2252 SEM / YEAR : II year SUBJECT NAME : COMMUNICATION THEORY UNIT

More information

Advances in Widely Tunable Lasers Richard Schatz Laboratory of Photonics Royal Institute of Technology

Advances in Widely Tunable Lasers Richard Schatz Laboratory of Photonics Royal Institute of Technology Advances in Widely Tunable Lasers Richard Schatz Laboratory of Photonics Royal Institute of Technology Tunability of common semiconductor lasers Widely tunable laser types Syntune MGY laser: tuning principle

More information

AM, PM and FM mo m dula l ti t o i n

AM, PM and FM mo m dula l ti t o i n AM, PM and FM modulation What is amplitude modulation In order that a radio signal can carry audio or other information for broadcasting or for two way radio communication, it must be modulated or changed

More information

Modulation is the process of impressing a low-frequency information signal (baseband signal) onto a higher frequency carrier signal

Modulation is the process of impressing a low-frequency information signal (baseband signal) onto a higher frequency carrier signal Modulation is the process of impressing a low-frequency information signal (baseband signal) onto a higher frequency carrier signal Modulation is a process of mixing a signal with a sinusoid to produce

More information

Photomixer as a self-oscillating mixer

Photomixer as a self-oscillating mixer Photomixer as a self-oscillating mixer Shuji Matsuura The Institute of Space and Astronautical Sciences, 3-1-1 Yoshinodai, Sagamihara, Kanagawa 9-8510, Japan. e-mail:matsuura@ir.isas.ac.jp Abstract Photomixing

More information