Chapter 9 Zero-Voltage or Zero-Current Switchings

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1 Chapter 9 Zero-Voltage or Zero-Current Switchings converters for soft switching 9-1

2 Why resonant converters Hard switching is based on on/off Switching losses Electromagnetic Interference (EMI) because of high du/dt and di/dt SMPS size decreses with increasing switching frequency Target is to use as high f s as possible Switching losses are reduced if voltage and/or current are zero during switching 9-2

3 One Inverter Leg The output current can be positive or negative 9-3

4 Hard Switching Waveforms The output current can be positive or negative 9-4

5 Change over T- conducts I o and it is turned off Voltage over it increases and when it is U d diode D+ starts to conduct Because of parasitic inductances voltage exceeds U d D+ conducts I o and T- is turned on Current increares and exceeds I o because of diode reverse recovery current After recovery of the diode voltage over T- drops to nearly zero 9-5

6 Turn-on and Turn-off Snubbers Turn-off snubbers are used, turn-on very seldom 9-6

7 Switching Trajectories Comparison of Hard versus soft switching 9-7

8 Switching losses Voltage and current stresses of the switches can be reduced by snubber circuits (Finnish kytkentäsuojapiiri) Losses are transferred from the switch to the R of the RC-snubber C discharges through R when switch is turned on Total losses do not necessarily decrease, requires careful dimensioning In resonant circuit switching losses in theory can be even zero 9-8

9 Basics of resonant circuits Series resonance Lossless parallel resonant circuit 9-9

10 Undamped Series-Resonant Circuit The waveforms shown include initial conditions 9-10

11 Series resonance Equations Solution from time t = 0 i L = I L0 cos 0 t + V d V C0 Z 0 di du L u U C i dt dt L C r C d r L sin 0 t Resonance frequency and impedance v C = V d V d V C0 cos 0 t + Z 0 I L0 sin 0 t f 0 Z 0 = L r C r L r C r Often per unit values are used V base = V d I bas e = V d Z

12 Series-Resonant Circuit with Capacitor-Parallel Load The waveforms shown include initial conditions 9-12

13 Series-Resonant Circuit with Capacitor- Parallel Load Equations Derivation i C = C dv C r dt = L rc d2 i L r dt 2 And using d 2 i L dt 2 Solution is i L = 0 2 I o v C = V d L r di L dt i L i C = I o i L = I o + I L0 I o cos 0 t + V d V C0 Z 0 sin 0 t v C = V d V d V C0 cos 0 t + Z 0 I L0 I o sin 0 t 9-13

14 Impedance of a Series-Resonant Circuit Quality factor Q = 0 L r R = 1 0 C r R = Z 0 R The impedance is capacitive below the resonance frequency 9-14

15 Undamped Parallel-Resonant Circuit i L + C r dv C dt = I d v C = L r di L dt i L = I d + I L0 I d cos 0 t + V C0 Z 0 sin 0 t v C = V C0 cos 0 t + Z 0 I d I L0 sin 0 t 0 = 2šƒ 0 = 1 L r C r Z 0 = L r C r 9-15

16 Impedance of a Parallel-Resonant Circuit Q = 0 R C r = R = 0 L R r Z 0 The impedance is inductive below the resonant frequency At resonance frequency imaginary part of admittance is zero, i.e. impedance is infinite 9-16

17 Load resonant converters Series Load Resonant (SLR) Converter Discontinuous area s < 0 /2 Continuous area 0 /2 < s < 0 Continuous area s > 0 Steady state characteristics Control of SLR Parallel Load Resonant (PLR) Converter Discontinuous area Continuous area s < 0 Continuous area s > 0 Steady state characteristics Hybrid-resonant converter 9-17

18 Load resonant converters Converter has LC-resonant circuit and load current goes through it Both series and parallel resonance Voltages and current in the resonant circuit are introducing zero voltage or current switching Load power is controlled by adjusting switching frequency in relation to resonance frequency Impedance of the resonant circuit changes 9-18

19 Series Load Resonant (SLR) Converter The transformer is ignored in this equivalent circuit 9-19

20 Principle Full-bridge and transformer connection are also possible Current of the resonant circuit is rectified in the diode bridge Output voltage U o is assumed to be constant and its polarity depends on the sign of current i L of the resonant circuit 9-20

21 Polarity of voltages Positive current U U T conducts johtaa u u U 2 2 d d AB AB o U U D conducts johtaa u u U 2 2 d d AB AB o Negative current U U T conducts johtaa u u U 2 2 d d AB AB o U U D conducts johtaa u u U 2 2 d d AB AB o 9-21

22 SLR Waveforms, DCM, s < 0 /2 9-22

23 Operation Current of T+ is zero Turned on at 0 t 0 At 0 t 1 current of resonant circuit turns and D+ conducts, because T- is not turned on yet ( s < 0 /2) After 180, at 0 t 2 current goes to zero Because of symmetry, capacitor voltage is 2U o Because 2U o < U d /2 + U o inductor current is not increasing but it is discontinuous At 0 t 3 control is given to T- and negative half cycle starts 9-23

24 Remarks Switches are turnig of naturally as current goes to zero Even thyristors could be used Switches are turning on when current is zero but voltage not Peak value of current in the resonant circuit is much higher than the average of output current 9-24

25 SLR Waveforms, CCM, 0 /2 < s <

26 Operation Switch T+ current 0 It is turned on at 0 t 0, voltage is U d Switch conducts less than 180 At 0 t 1 current i L becomes negative and D+ conducts T- is turned on at 0 t 2 This is earlier than in the previous DCM operating area s < 0 /2 D+ conducts less than

27 Devices Turning on Current and voltage are not zero => losses Turning off Current and voltage are zero Even thyristors could be used Reverse recovery current of the diodes must be small 9-27

28 SLR Waveforms, CCM, s >

29 Operation Current of T+ is zero and it is turned on at 0 t 0 T+ is turned on at 0 t 1 This is before the current has become zero D- starts to conduct Voltage over the LC-circuits is high and diode current goes rapidly to zero T- is turned on immeadiately as D- starts to conduct T- can conduct as the polarity of the current changes 9-29

30 Switches Turn-on at zero current and voltage Turning off takes place close to the peak of the resonant current Turn-off losses Before the switch starts to conduct the antiparall diode has conducted Voltage over switch is 0 It is possible to use lossless snubbers, i.e. only snubber capacitor in the circuit as there is no discharge current when the switch is turned on 9-30

31 Lossless Snubbers in SLR Converters The operating frequency is above the resonance frequency 9-31

32 SLR Converter Characteristics Output Current as a function of operating frequency for various values of the output voltage 9-32

33 SLR Converter Control The operating frequency is varied to regulate the output voltage In full-bridge converters frequency can also be constant and voltage is controlled phase-shifting leg voltages, ( D = 50 %) 9-33

34 Parallel Load Resonant (PLR) Converter The transformer is ignored in this equivalent circuit 9-34

35 Principle Voltage of C r is recitified and filtered Output current is assumed to be constant during switching cycle Voltage over the resonant circuit U u d AB 2 T tai or D U u d AB 2 T tai or D johtaa conducts johtaa Operation depends on i L conducts and u C 9-35

36 PLR Waveforms, DCM The current is in a discontinuous conduction mode 9-36

37 Operation (1/2) T+ is turned on at 0 t 0, i L = u C = 0 Constant output current flows through the diode bridge and keeps capacitor voltage as zero After 0 t 1 current difference charges resonant capacitor LC-circuit current i L goes to zero at 0 t 2 and becomes negative D+ conducts as T- is not turned on 9-37

38 Operation (2/2) Gate of T+:n is removed before 0 t 3 :a i L remains zero Cr discharges in time 0 (t 3 t 4 ) with I o After this we are in the beginning Output voltage average is adjusted with time t 5 t 4 No turn-on or turn-off losses in diodes 9-38

39 PLR Waveforms, CCM, s < 0 The operating frequency is below the resonance frequency 9-39

40 PLR Converter Waveforms, CCM, s > 0 The operating frequency is above the resonance frequency 9-40

41 PLR, CCM No trun-on losses Turn-off with current Losses Losses can be reduced with lossless snubber as in SLR 9-41

42 PLR Converter Characteristics Output voltage as a function of operating frequency for various values of the output current 9-42

43 PLR Characteristics DCM Output voltage doesn t depend on current Many parallel outputs are possible Output voltage depends linearly from switching frequency Output voltage can be higher than input Maximum current and voltage much higher than I o and U d 9-43

44 PLR versus SLR PLR Acts as voltage sourc Fits for multiple output SMPS No built in overload protection Both step up and step down operation 9-44

45 Hybrid-Resonant DC-DC Converter Combination of series and parallel resonance 9-45

46 Parallel-Resonant Current-Source Converter Basic circuit to illustrate the operating principle at the fundamental frequency 9-46

47 Parallel-Resonant Current-Source Converter Using thyristors; for induction heating 9-47

48 Class-E Converters Optimum mode 9-48

49 Class-E Converters Non-Optimum mode 9-49

50 Resonant Switch Converters Classifications 9-50

51 Resonant Switch Converters Similar ideas was used before gate turnoff devices Thyristors were used in dc-dc converters and dc-ac inverters => additional LC circuit used to turn-off conduction thyristor (e.g. McMurray-circuit) Nowadays also in power supplies Transformer parasitic inductances and other parasitics can be used in LC-circuits 9-51

52 Classification ZCS, zero-current-switching Switch turns on and off without current ZVS, zero-voltage-switching Switch turns on and off without voltage ZVS-CV, zero-voltage-switching, clamped voltage As before but at least two switches Voltage over switch is limited to the supply voltage 9-52

53 ZCS Resonant-Switch Converter 9-53

54 Operation principle Current I o goes through the diode C r is charged to the supply voltage U d Switch is turned on Diode D conducts untill at t 1 current is equal to the load current L r C r is a resonant circuit discharging C r At t 2 current goes to zero and switch turns off Output current I o charges C r to the supply voltage At t 3 diode starts to conduct 9-54

55 ZCS Resonant-Switch Converter Waveforms; voltage is regulated by varying the switching frequency, time interval t 4 - t

56 Properties Resonant frequency in MHz area resonanssitaajuus valitaan MHz-alueelle Switch turns on and off without current At turn-off switch voltage is U d => turn-off losses Output current I V Z, Z L C o o 0 0 r r When output current increases output voltage decreases Switching frequency is increased Antiparallel connected diode At low load resonant circuit energy can be supplied back to the supply 9-56

57 Electromagnetic Interference, EMI Losses and EMI due to the converter are reduced when soft switching is used Peak current of switch High when compared to the output current Conduction losses are higher than in hard switching EMI increases??? 9-57

58 ZCS Resonant-Switch Converter A practical circuit Capacitor is in parallel with the diode 9-58

59 Operation When switch is turned on its current increases linearly untill i T = I o Diode turns off Current i T I o charges capacitor after t 1 At t 2 current i T goes to zero and switch turns off Capacitor is discharged with output current 9-59

60 ZVS Resonant-Switch Converter Capacitor is connected in paralle with the switch => limits voltage changes Serious limitations 9-60

61 Operation Switch is turned off when it conducts I o Capacitor C r charges with constant current At t 1 u C = U d Diode D conducts, C r L r resonant circuit At t 2 C r voltage becomes zero D r starts to conduct, gate control is given to switch and current i L increases linearly A t 2 current is positive and it goes through the switch At t 3 i L is equal to I o and D stops to conduct 9-61

62 ZVS Resonant-Switch Converter Output voltage 9-62

63 Comparison of ZCS and ZVS ZCS Switch maximum current Output current limited ZVS Switch maximum voltage I V Z Output current must be larger than High voltage switch is needed if output power variation is large o d 0 I V Z, Z L C o o 0 0 r r V d I Z o 0 Vd Z

64 MOSFET Internal Capacitances These capacitances affect the MOSFET switching ZVS is better for MOSFET ZCS good e.g. for IGBT s because of tail current 9-64

65 Zero-voltage-switching, clamped-voltage, ZVS- CV The inductor current must reverse direction during each switching cycle 9-65

66 ZVS-CV Switch turn on and off with zero voltage Maximum voltage is clamped to input voltage L f is small when compared to hard switching Its current is both positive and negative T+ conduct current and it is turned off Voltage over it is zero because of C

67 ZVS-CV DC-DC Converter One transition is shown In Fig c) C + = C = C/2 i L is not change much during t 0 - t

68 Operation (1/2) Condensator C has discharged at t 0 Inductor s current decreases linearly as D- conducts and u L = -U o. At the same time gate control to T- When current polarity changes at t 0 switch starts to conduct T- is turned of at t 1 with zero voltage (u C- = 0) When C - is charged to U d and C + has discharged, negative current flows through diode D+ 9-68

69 Operation (2/2) After t 1 voltage over inductor is positive Its current is positive after t 2 when T+ conducts For ZVS capacitor is connected parallel to the switch Capacitor must be discharged when switch is turned on It is discharged if antiparallel diode has been conducting Therefore current i L has to have both polarities 9-69

70 Control of output voltage Constant frequency PWM can be used Durations t 0 - t 0 and t 1 t 1 can be assumed short Output voltage is square wave => U o D U d L f must be dimensioned so that Even with smallest U d and highes load current instantaneous value of i L is also negative 9-70

71 ZVS-CV Principle Applied to DC-AC Inverters Even in dc-dc converter inductor current had negative values, now both polarities are equal Very large ripple in the output current 9-71

72 Control of output voltage In full bridge delay between pole voltages can be adjusted 9-72

73 Three-Phase ZVS-CV DC-AC Inverter Very large ripple in the output current 9-73

74 ZVS-CV with Voltage Cancellation Commonly used Lm is magnetizing inductance of transformer 9-74

75 Resonant DC-Link Inverter The dc-link voltage is made to oscillate 9-75

76 Three-Phase Resonant DC-Link Inverter Modifications have been proposed 9-76

77 High-Frequency-Link Inverter Basic principle for selecting integral half-cycles of the high-frequency ac input 9-77

78 High-Frequency-Link Inverter Low-frequency ac output is synthesized by selecting integral half-cycles of the high-frequency ac input 9-78

79 High-Frequency-Link Inverter Shows how to implement such an inverter 9-79

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