GX434 Monolithic 4x1 Video Multiplexer

Transcription

1 Monolithic x Video Multiplexer DATA SHEET FEATURES low differential gain: 0.0% typ. at. MHz low differential phase: 0.0 deg. typ. at. MHz low insertion loss: 0.0 db max at 00 khz low disabled power consumption:. mw typ. high off isolation: 0 db at 0 MHz all hostile MHz, db typ. bandwidth (-db) with 0 pf load, 00 MHz typ. fast make-before-break switching: 00 ns typ. TTL and volt CMOS compatible logic inputs low cost pin DIP and pin SOIC packages optimised performance for NTSC, PAL and SECAM applications APPLICATIONS Glitch free analog switching for... High quality video routing A/D input multiplexing Sample and hold circuits TV/ CATV/ monitor switching CIRCUIT DESCRIPTION The is a high performance low cost monolithic x video multiplexer incorporating four bipolar switches with a common output, a to address decoder and fast chip select circuitry. The chip select input allows for multi-chip paralleled operation in routing matrix applications. The chip is selected by applying a logic 0 on the chip select input. Unlike devices using MOS bilateral switching elements, these bipolar circuits represent fully buffered, unilateral transmission paths when selected. This results in extremely high output to input isolation. They also feature fast make-before-break switching action. These features eliminate such problems as switching 'glitches' and output-to-input signal feedthrough. The operates from ± to ±. volt DC supplies. They are specifically designed for video signal switching which requires extremely low differential phase and gain. Logic inputs are TTL and volt CMOS compatible providing address and chip select functions. When the chip is not selected, the output goes to a high impedance state. PIN CONNECTIONS IN PIN TOP VIEW +V AO A PIN TOP VIEW +V NC AVAILABLE PACKAGING pin DIP and pin SOIC (wide) IN O/P NC R EXT IN IN AO A O/P IN IN NC NC R EXT FUNCTIONAL BLOCK DIAGRAM PIN CONNECTION PIN DIP PIN CONNECTION PIN SOIC (wide) IN IN IN X X X X PUT TRUTH TABLE A A0 PUT IN 0 0 IN A TO DECODER LOGIC CHIP SELECT 0 IN X X HI - Z X = DON'T CARE Document No GENNUM CORPORATION P.O. Box, Stn A, Burlington, Ontario, Canada LR Y tel. (0) - fax: (0) - Japan Branch: A-0 M i yamae Village, 0 Mi yamae, Suginami ku, Tokyo, Japan tel. (0) -00 fax (0) -

2 ABSOLUTE MAXIMUM RATINGS ORDERING INFORMATION Parameter Supply Voltage Operating Temperature Range Storage Temperature Range Value & Units ±.V 0 C T A 0 C - C T S 0 C Part Number Package Type Temperature Range CDB Pin DIP 0 to 0 C CKC Pin SOIC 0 to 0 C CTC Tape Pin SOIC 0 to 0 C Lead Temperature (Soldering, 0 Sec) 0 C Analog Input Voltage Analog Input Current Logic Input Voltage +.V 0µA AVG, 0 ma peak V L +.V CAUTION ELECTROSTATIC SENSITIVE DEVICES DO NOT OPEN PACKAGES OR HANDLE DEVICES EXCEPT AT A STATIC-FREE WORKSTATION +Vcc 0.pF 0.pF 0.pF 0.pF IN 0.V.k # ma # #.pf +. V pf 00Ω + pf Common C pf Fig. Crosspoint Equivalent Circuit Fig. Disabled Crosspoint Equivalent Circuit ELECTRICAL CHARACTERISTI (V S = ±V DC, 0 C < T A < 0 C, C L = 0 pf, = 0kΩ unless otherwise shown.) PARAMETER SYMBOL CONDITIONS MIN TYP MAX UNITS Supply Voltage ±V S. V DC I+ Chip selected (=0) ma SUPPLY Chip not selected (=) ma Supply current I- Chip selected (=0) ma Chip not selected (=) ma Analog Output Extremes before clipping occurs V Analog Input Bias I BIAS - - µa Current STATIC Output Offset Voltage V OS T A = C, Ω resistor on each input to gnd 0 mv Output Offset Voltage V OS / T µv/ C Drift R EXT =. kω, % 0 - -

3 ELECTRICAL CHARACTERISTI continued (V S = ±V DC, 0 C < T A < 0 C,C L = 0pF, = 0kΩ unless otherwise shown.) PARAMETER SYMBOL CONDITIONS MIN TYP MAX UNITS Crosspoint Selection t ADR-ON Control input to appearance ns Turn-On Time of signal at the output. Crosspoint Selection t ADR-OFF Control input to disappear ns Turn-Off Time ance of signal at output. Chip Selection t -ON Control input to appearance ns Turn-On Time of signal at output. Chip Selection t -OFF Control input to disappear ns Turn-Off Time ance of signal at output. LOGIC Logic Input V IH V Thresholds V IL V Address Input I BIAS(ADR) Chip selected A0,A = µa Bias Current Chip selected A0,A = na Chip Select Bias I BIAS() = na Current = µa Insertion Loss I.L. V p-p sine or sq. wave at db 00 khz Bandwidth (- db) B.W MHz Gain Spread at MHz db -0.0 T = C, R = Ω Input to Output Signal t P A S ƒ=. MHz - - ± degrees Delay Matching (chip to chip) 0 C < T A < 0 C, R S as - - ±0. degrees above, ƒas above. Input Resistance Chip selected ( = 0) kω DYNAMIC Input Capacitance C IN Chip selected ( = 0) pf Chip not selected ( = ) -. - pf Output Resistance R Chip selected ( = 0) - - Ω Output Capacitance C Chip not selected ( = ) - - pf Differential Gain dg % at. MHz Differential Phase dp = 0 IRE, (Fig. ) degrees All Hostile Crosstalk X TALK (AH) Sweep on inputs V p-p (see graph) th input has 0 Ω resistor to - db gnd. ƒ = MHz (Fig. ) Chip Disabled Crosstalk X TALK(CD) db (see graph) ƒ = 0 MHz (Fig. ) Slew Rate +SR V/µs = V p-p (C L = 0 pf) -SR V/µs R EXT =.kω, % 0 - -

4 TYPICAL PERFORMANCE CURVES OF THE ALL HOSTILE CROSSTALK (db) GAIN (db) 0 pf 0 pf 0 pf 0 pf Load Capacitance Gain vs Frequency = Ω -0 =.Ω = 0Ω = 0 kω All Hostile Crosstalk ( pin DIP) ALL HOSTILE CROSSTALK (db) PHASE (DEGREES) Load Capacitance 0 pf 0 pf pf pf Phase vs Frequency = Ω = Ω =. Ω = 0 Ω = 0 kω SW / SW SW0 - SW All Hostile Crosstalk ( pin SOIC) For all graphs, V S = ± V DC and T A = C. The curves shown above represent typical batch sampled results

5 0 CHIP DISABLED CROSSTALK (db) Chip Disabled Crosstalk vs Frequency CHIP DISABLED CROSSTALK (db) Analog signal IN is 0 IRE ( mv p-p) at 0 MHz INPUT BIAS (V) Chip Disabled Crosstalk vs Input Bias (V) DIFFERENTIAL PHASE & GAIN (DEGREES & %) ƒ =. MHz Blanking level is clamped to V BIAS dg % INPUT BIAS (V) dp dg/dp vs Input Bias DIFFERENTIAL PHASE & GAIN (DEGREES & %) dg % dp. dg/dp vs Frequency Blanking level 0V DC MΩ MΩ +0. OFF GAIN SPREAD (db) GAIN SPREAD (db) MΩ 00 kω ON C IN OFF C IN ON INPUT CAPACITANCE (pf) INPUT CAPACITANCE (pf) Normalized Gain Spread C L = 0pF 0 kω INPUT BIAS (V) Input Impedance 0 - -

6 V/div 0 mv/div Fig. 0. µs/div µs/div Switching Transient (crosspoint to crosspoint) Fig. Switching Envelope (crosspoint to crosspoint) Chip disabled crosstalk = 0 log All hostile crosstalk = 0 log ENABLED CROSSPOINT 0 kω. Ω Fig. Chip Disabled Crosstalk Test Circuit Fig. All Hostile Crosstalk Test Circuit BLANKING LEVEL 0 µh 0 µh LUMINANCE LEVEL V CONTROL BIT FROM I/O PORT R.F. SIGNAL SOURCE Ω. kω 0 Ω RELAY SWITCH 0 Ω 0 Ω DUT µf AC COUPLING C L BUFFER AMP x Ω Ω Fig. Differential Phase and Gain Test Circuit DIFFERENTIAL GAIN AND PHASE TEST CIRCUIT The test circuit of Figure allows two DC bias levels, set by the user, to be superimposed on a high frequency signal source. A computer controlled relay selects either the preset blanking or luminance level. One measurement is taken at each level and the change in gain or phase is calculated. This procedure is repeated one hundred times to provide a reasonably large sample. The results are averaged to reduce the standard deviation and therefore improve the accuracy of the measurement. The output from the device under test is AC coupled to a buffer amplifier which allows the buffer to operate at a constant luminance level so that it does not contribute any dg or dp to the measurement

7 OPTIMISING THE PERFORMANCE OF THE. Power Supply Considerations Table shows the effect on differential gain (dg) and differential phase (dp) of various power supply voltages that may be used. A nominal supply voltage of ± volts result in parameter values as shown in the top row of the table. By using other power supply voltage combinations, improvements to these parameters are possible at the sacrifice of increased chip power dissipation. Maximum degradation of the differential gain and phase occurs for the last combination of +, - volts along with an increase in power dissipation; these voltages are not recommended. Supply Differential Gain Differential Phase Voltage % degrees (Typical) (Typical) ± / ± / Table shows the general characteristic variations of the when different combinations of power supply voltages are used. These changes are relative to a circuit using ± volts Vcc. Supply Voltage Characteristic Changes ± - lower logic thresholds - max logic I/P (.V) - loss of off isolation ( 0 db) - poorer dg and dp +/ - - slight increase in negative supply current - slight decrease in offset - very similar frequency response - better dg and dp ± - increase in supply current (0%) - increase in offset ( - mv) - very similar frequency response - better dg and dp The does not require input DC biasing to optimise dg or dp nor does it need switching transient suppression at the output. Furthermore, both the analog signal and logic circuits within the chip use one common power supply, making power supply configurations relatively simple and straightforward. Several of the input characteristic graphs on pages - show that for best operation, the input bias should be 0 volts. The switching transient photographs on page show how small the actual transients are and clearly show the make-beforebreak action of the video multiplexer switch. +/ - - loss in off isolation ( 0 db) - poorer dg and dp 0 - -

8 . Load Resistance Considerations The crosspoint switch is optimised for load resistances equal to or greater than kω. Figure shows the effect on the differential gain and phase when the load resistance is varied from 00 Ω to 00 kω. DIFFERENTIAL PHASE & GAIN (DEGREES & %) dp dg ƒ=. MHz, 0 IRE BLANKING LEVEL = 0V DC K 0K 00K (Ω) Fig. dg/dp vs. Multi-chip Considerations Whenever multi-chip bus systems are to be used, the total input and output capacitance must be carefully considered. The input capacitance of an enabled crosspoint (chip selected), is typically only pf and increases slightly to. pf when the chip is disabled. The total output capacitance when the chip is disabled is approximately pf per chip. Usually the multiplexer switch is used in a matrix configuration of (n x ) crosspoints perhaps combined in an (n x m) total routing matrix. This means for example, that four ICs produce a x configuration and have a total output capacitance of x pf or 0 pf if all four chips are disabled. For any one enabled crosspoint, the effective load capacitance will be x pf or pf. In a multi-input/multi-output matrix, it is important to consider the total input bus capacitance. The higher the bus capacitance and the more it varies from the ON to OFF condition, the more difficult it is to maintain a wide frequency response and constant drive from the input buffer. A x matrix using ICs ( x ), would have a total input bus capacitance of x. pf or 0 pf. The negative slew rate is dependant upon the output current and load capacitance as shown below. -SR = I + ma I ma C L The current I is determined from the following equation: I = EE R k Ω R It is possible to increase the negative slew rate (-S.R.) and thus the large signal bandwidth, by adding a resistance from the output to - V EE. This resistor increases the output current above the ma provided by the internal current generator and increases the negative slew rate. The additional slew rate improving resistance must not be less than kω in order to prevent excessive currents in the output of the device. An adverse effect of utilising this negative slew rate improving resistor, is the increase in differential phase from typically 0.00 to 0.0. Under these same conditions, the differential gain drops from typically 0.0 % to 0.0 %. +V 0 I N P U T B U F F E R S IN IN IN A0 A 0 PUT NC R kω n O U T P U T B U F F E R S m Fig. Negative Slew Rate (-SR) Improvement Fig.0 Multi-chip Connections 0 - -

9 APPLICATIONS INFORMATION The multiplexer is a very high performance, wideband circuit requiring careful external circuit design. Good power supply regulation and decoupling are necessary to achieve optimum results. The circuit designer must use proper lead dress, component placement and PCB layout as in any high frequency circuit. Functionally, the video switches are non-inverting, unity gain bipolar switches with buffered inputs requiring DC coupling and Ω line terminating resistors when directly driven from Ω cable. The output must be buffered to drive Ω lines. This is usually accomplished with the addition of an operational amplifier/ buffer which also allows adjustments to be made to the gain, offset and frequency response of the overall circuit. A typical video routing application is shown in Figure. Four ICs are used in a x multiplexer switching circuit. An external address decoder is shown which generates the address and chip enable codes from a binary number. The address inputs to each chip are active high while the chip select inputs are active low. Depending on the application and speed of the logic family used, latches may be required for synchronization where timing and delays are critical. Since the individual crosspoint switching circuits are unidirectional bipolar elements, low crosstalk and high isolation are inherent. The makebefore-break switching characteristics of the means virtually 'glitch' free switching. VIDEO INPUTS SWITCHES +V BINARY ADDRESS DECODER V 0 V V V V V V V V V V 0 V V V V V IN IN IN IN IN IN Fig. IN IN IN IN IN IN +V A 0 R EXT +V A 0 R EXT +V A 0 R EXT +V A R EXT 0 +V +V +V K % K % K % K % All resistors in ohms, all capacitors in microfarads unless otherwise stated. x Video Multiplexer Circuit 0-0pF HC A A A +V +V ENABLE 0 DOCUMENT IDENTIFICATION Video Out CLC 0 (comlinear) PRODUCT PROPOSAL This data has been compiled for market investigation purposes only, and does not constitute an offer for sale. ADVANCE INFORMATION NOTE This product is in development phase and specifications are subject to change without notice. Gennum reserves the right to remove the product at any time. Listing the product does not constitute an offer for sale. PRELIMINARY DATA SHEET The product is in a preproduction phase and specifications are subject to change without notice. DATA SHEET The product is in production. Gennum reserves the right to make changes at any time to improve reliability, function or design, in order to provide the best product possible. Gennum Corporation assumes no responsibility for the use of any circuits described herein and makes no representations that they are free from patent infringement. Copyright August Gennum Corporation. Revision date: January. All rights reserved. Printed in Canada