SVPWM Overmodulation Scheme of Three-Level Inverters for Vector Controlled Induction Motor Drives

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1 SVPWM Overmodulation Scheme of Three-Level Inverter for 481 JPE ICPE 07 Selected Paper SVPWM Overmodulation Scheme of Three-Level Inverter for Vector Controlled Induction Motor Drive Kyoung-Min Kwon, Jae-Moon Lee, Jin-Mok Lee, and Jaeho Choi School of Electrical and Computer Engineering, Chungbuk National Univerity, Cheongju, Korea R&D Center, LS Indutrial Sytem Co. Ltd., Cheonan, Korea ABSTRACT Thi paper decribe a SVPWM overmodulation cheme of NPC type three-level inverter for traction drive which extend the modulation index from MI=0.907 to unity. SVPWM trategy i organized by two operation mode of under-modulation and over-modulation. The witching tate under the under-modulation mode are determined by dividing them with two linear region and one hybrid region the ame a the conventional three-level inverter. On the other hand, under the over-modulation mode, they are generated by doing it with two over-modulation region the ame a the conventional over-modulation trategy of a two level inverter. Following the decription of over-modulation cheme of a three-level inverter, the ytem decription of a vector controlled induction motor for traction drive ha been dicued. Finally, the validity of the propoed modulation algorithm ha been verified through imulation and experimental reult. Keyword: Overmodulation, SVPWM, NPC type three-level inverter, Indirect vector control 1. Introduction Thi paper preent an overmodulation cheme of NPC type three-level inverter and an indirect vector control of induction motor for traction drive. Recently railway vehicle have operated at higher peed within the limited plant for higher efficiency. The conventional railway vehicle ha ued the vector control to the modulation factor of 90.7% with pace vector PWM (SVPWM) and ued the lip-frequency control to ix-tep mode. The lip-frequency Manucript received January 0, 2009; revied April 8, 2009 Correponding Author: Tel: , Fax: , Chungbuk Nat l Univ. School of Electrical and Computer Engineering, Chungbuk National Univerity, Cheongju, Korea R&D Center, LS Indutrial Sytem Co. Ltd., Cheonan, Korea control i uitable for traction drive, becaue the drive pattern of electric railway ytem do not requet a rapid change. However, that control can not realize a quick torque repone. In high-peed train, the lip between train wheel and rail i likely to occur, and the fat torque control i crucial to overcome thi lip problem. The vector control provide an intantaneou torque repone becaue it i poible to control the flux and torque of the induction motor independently. An overmodulation cheme of SVPWM with modulation factor 90.7% to unity i eential if the drive can meet the operation at extended peed including the field weakening region in vector control with higher torque and power characteritic. The overmodulation trategy of a two-level inverter and it implementation ha been tudied [1,2]. The NPC type three-level inverter ha three output voltage

2 482 Journal of Power Electronic, Vol. 9, No., May 2009 level. With thi circuit configuration, the voltage tre on it power witching device i half that of the conventional two-level inverter. Becaue of thi nature, it ha been applied to the medium and high voltage drive. In addition to the capability to handle the high voltage, the NPC type three-level inverter ha favorable feature; lower line to line and common-mode voltage tep, more frequent voltage tep in one carrier cycle, and lower ripple component in the output current at the ame carrier frequency. Thee feature lead to ignificant advantage for motor drive over the conventional two-level inverter in the form of lower tree to the motor winding and bearing, le influence of noie to the adjacent equipment, etc []. Recently, mot Japanee electrical train companie have developed a three-level PWM inverter drive ytem for traction drive. It i well known that the three-level configuration ha greatly reduced the ize of the main tranformer and traction-motor, the current harmonic in the ignaling band, the acoutic noie, and the volume and weight of the equipment [4]-[7]. Alo, the power rating of the ytem can be increaed. However, SVPWM of a three-level inverter i coniderably more complex than that of a two-level inverter due to the large number of inverter witching tate. Beide, there i the problem of neutral point voltage balancing [8]. There have been ome tudie on the over-modulation trategy of three-level inverter, but few of them are focued on the application of traction drive. Mot of them are limited to the modulation itelf and lack of experimental implementation [9]-[11]. Thi paper decribe a SVPWM over-modulation cheme of the NPC type three-level inverter that extend the modulation index from MI=0.907 to unity [12]. SVPWM trategy i organized by two operation mode of under-modulation and over-modulation. The witching tate under the under-modulation mode are determined by dividing them with two linear region and one hybrid region the ame a the conventional three-level inverter. On the other hand, under the over-modulation mode, they are generated by doing thi with two over-modulation region which i the ame a the conventional over-modulation trategy of the two level inverter. Following the decription of the over-modulation cheme of the three-level inverter, the ytem decription of a vector controlled induction motor for traction drive ha been dicued. Finally, the validity of the propoed modulation algorithm ha been verified through the imulation and experimental reult. 2. NPC type Three-level Inverter The NPC type three-level inverter ha three output voltage level. With thi circuit configuration, the voltage tre on it power witching device i half that of the conventional two-level inverter. Becaue of thi nature, it ha been applied to the medium and high voltage drive. In addition to the capability to handle the high voltage, the NPC type three-level inverter ha favorable feature; lower line to line and common-mode voltage tep, more frequent voltage tep in one carrier cycle, and lower ripple component in the output current at the ame carrier frequency. Thee feature lead to ignificant advantage for motor drive over the conventional two-level inverter in the form of lower tree to the motor winding and bearing, le influence of noie to the adjacent equipment, etc. Fig. 1 how the chematic diagram of a three-level IGBT inverter with induction motor load. For power converion, a imilar unit i connected at the DC input in an invere manner. The phae U, for example, get the tate P when the witche U1 and U2 are on, wherea it get the tate N when the witche U and U4 are on. At neutral-point clamping, the phae get the O tate when either U2 or U conduct depending on poitive or negative phae current polarity, repectively. The witching tate of the three-level inverter can be ummarized a hown in Table 1, where U, V, and W are the phae and P, N, and O are dc-bu point. The total witching tate conit of 27 and can be Vdc Gate_U1 Gate_V1 Gate_W1 Vc_UP Gate_U2 Gate_V2 Gate_W2 Vc_DN Gate_U Gate_U4 Gate_V Gate_V4 Gate_W Gate_W4 Fig. 1. Schematic diagram of three-level inverter with induction motor load. IM

3 SVPWM Overmodulation Scheme of Three-Level Inverter for 48 decribed a hown in Fig. 2. The correponding 27 witching tate of the three-level inverter indicating each tate with the combination of P, N, and O tate are claified by four voltage vector according to the magnitude value of voltage vector. The four voltage vector are eparated by zero vector (ZV), mall vector (SV), middle vector (MV), and large vector (LV). Thee four voltage vector are ummarized in Table 2. Evidently, neutral current will flow through the point O in all the tate except the zero tate and the outer hexagon ha ix large ector(a-f) a hown and each large ector ha four mall ector(1-4), giving altogether 24 region of operation. An overmodulation trategy for higher voltage utilization i driven from the developing Fourier erie expanion of the reference phae voltage waveform which generate the deired fundamental component. According to the modulation index (MI), the PWM control range can be divided into three region a one linear region ( 0 MI 0.907) of undermodulation mode and two overmodulation mode of overmodulation region I ( MI 0.952) and overmodulation region II ( MI 1) a hown in Fig.. 10 NPO OPO NON OPP NPP NOO OOP NOP NNO 16 Sector D Sector C Sector B NPN OPN PPN PPO OON 5 1 PPP POO OOO ONN NNN 21 PON 17 2 POP ONO PNO NNP ONP PNP Sector E Sector A 2 PNN 24 Fig. 2. Space voltage vector diagram of NPC type three-level Inverter. Over Modulation Region V8 V6 V5 Linear Region II V9 V7 Hybrid Region V4 V Linear Region I V11 V10 V0 V1 V2 V12 V1 V16 V18 Sector F Table 1 Switching tate of three-level inverter V14 V15 V17 Switching State Gate-(X) X=[U, V, W] V(X)O [Node voltage] X-1 X-2 X- X-4 Fig.. Operation region of three-level inverter for overmodulated PWM. P ON ON OFF OFF 2 O OFF ON ON OFF 0 N OFF OFF ON ON 2 Switching SV vector Table 2 Voltage vector according to witching tate Switching tate (U V W) Capacitor tate V C _ UP V C _ DN voltage vector ZV (PPP) (OOO) (NNN) MV LV USV LSV (POO) (PPO) (OPO) (OPP) (OOP) (POP) (ONN) (OON) (NON) (NOO) (NNO) (ONO) (PON) (OPN) (NPO) (NOP) (ONP) (PNO) (PNN) (PPN) (NPN) (NPP) (NNP) (PNP) /- +/- +/- +/- 2V dc 2.1 Undermodulation mode ( 0 MI ) The linear region i located in the incribed circle of an outer hexagon. It conit of linear region mode I ( 0 MI 0.4), linear region II ( 0.5 MI 0.907), and their interfaced hybrid region ( 0.4 MI 0.5). Linear region mode I i located in the incribed circle of inner hexagon. The Hybrid region i located between the incribed circle of inner hexagon and the circumcribed circle of the inner hexagon. Linear region mode II i located between the circumcribed circle of inner hexagon and the incribed circle of outer hexagon. Linear region mode I ha tep output line-to-line voltage like a 2-level inverter. Linear region mode II ha 5 tep output line-to-line voltage. And hybrid region ha the characteritic of linear region mode I and linear region mode II.

4 484 Journal of Power Electronic, Vol. 9, No., May 2009 V0 Tb θ e V4 Tc mall ector 1 Sector A V V1 Ta V5 Ta mall ector 4 mall ector V Tb mall ector 2 Fig. 4. Voltage vector in large ector A. Table Duration time of voltage vector in each mall ector mall ector T a T b 1 2kT in( e) T[1 2k in( e )] 2 2T [1 k in( e )] V2 Tc T c 2 kt in 2 kt in e T [ 2k in( e ) 1] T[ 1 2k in e ] T [ 2 in( k e ) 1] T [ 2 in( k e ) 1] 4 T[ 2k in e 1] 2kT in( e) 2T [1 k in( e )] T : ampling time for reference vector k V Vdc 2 MI : modulation amplitude ratio Figure 4 how one of ix large ector in the linear region. Each large triangle can be divided into four mall ector 1, 2,, and 4. In SVPWM method, the inverter voltage vector correponding to the apexe of the triangle which include the voltage reference vector are generally elected to minimize the harmonic component of the output line-to-line voltage. Table how the analytical time expreion for all the mall ector in the large ector A. Thee time interval can be applied to the other large ector by a phae hift of the voltage reference vector. Thee time interval are ditributed appropriately o a to generate the ymmetrical PWM pule with a neutral-point voltage balancing. Note that the equence in oppoite ector (A-D, B-E and C-F) i elected to be of a complimentary nature for the voltage balancing of a neutral-point. 2.2 Overmodulation mode ( MI 1) 1) Over-modulation region I ( MI ) e In the over-modulation region I, the voltage reference vector V exceed the outer hexagon which i the boundary of making a maximum voltage value. So V i booted up to V c for the compenation of voltage lo due to the exce region. Figure 5 preent the trajectory of V, V, and V which i the actual reference vector applying to control in the time domain. The angle r i the reference angle which i an interection of V c and boundary of the hexagon. The region of V r preent four kind of equation per /2 for the angle of the voltage reference vector, a hown in (1) to (4). In both ide region of each triangle ector to c r, V c i ued to compenate the voltage lo due to the exce of the outer hexagon. Plu it generate the maximum voltage value to follow the outer hexagon between thoe two region. The value of taking the fundamental component of Vr i directly proportional to MI. Im Vr i preented in Fig.. f1 tan, 0 r (1) 6 f 2 in, r r co r r (2) f in, r r () co 6 2 f 4 in, co r 6 V c ` V α r θ V r α r Re 2/Vdc 1/Vdc r (4) 2 2 f 1 f 2 A B 0 -α 6 r 6 +α 6 r f f 4 C D -α r 2 2 θ=ωt Fig. 5. Trajectory of reference voltage vector and phae voltage waveform in over-modulation region I.

5 SVPWM Overmodulation Scheme of Three-Level Inverter for 485 where e t and e i an angular velocity of the voltage reference vector. Expanding from (1) to (4) in the Fourier erie and taking it fundamental component, the reultant equation can be expreed a 4 F( r ) f d f d f d f d A 1 in B 2 in C in D 4 in (5) where A, B, C and D denote integral range of each voltage function a hown in Fig. 4. Since F( r ) repreent the peak value of the fundamental component, it can be calculated from the definition of the modulation index. 2 F( r ) Vdc MI (6) Thu, a relationhip between the MI and the reference angle which give a linearity of the output voltage i determined. The equation of the piecewie-linear reference angle ( r ) a a function of the MI i hown from (7) to (9). 0.2 MI MI (7) r MI MI (8) r 26.4 MI MI (9) r A etablihed in Fig. 4, the upper limit in the over-modulation region I i r 0. MI at thi condition i 0.952, which i driven in (5) and (6). Therefore when the MI i higher than 0.952, another over-modulation algorithm i neceary. 2) Over-modulation region II ( MI 1) Under uch condition, output voltage higher than MI=0.952 can not be generated ince there exit no more urplu area to compenate for the voltage lo even though the modulation index i increaed above that point. A a reult, over the compenation limit by uing the technique in the over-modulation region I, angle V r i held during holding h for the compenation of voltage lo when V i rotating according to time. Thi i called over-modulation region II. To control the holding angle of the time interval, the active witching tate remain at the vertice which uniquely control the fundamental voltage. A baic concept of the over-modulation region II i imilar to (5) and (6). Region of V r preent four kind of equation per /2 a the angle of reference voltage vector, h, a hown from (10) to (1). The value of the fundamental component of Vr i directly proportional to MI. Figure 6 how the trajectory of the reference voltage vector and phae voltage waveform in the overmodulation region II. 1 tan p h 6 f 0 (10) f2 h h (11) 6 6 ' f in p h h (12) ' co p f4 where h (1) 2 2 ' 6 ' ' p and p ( 1 h) (14) 6 h 6 In (14), ' p and p are phae angle of the actual voltage reference vector rotating a hown in Fig. 7, which i imply driven from the proportional relationhip for angular diplacement of thee two vector a : p : h. (15) 6 6 Thereafter, the actual voltage reference vector i held at the vertex while the fundamental one i continuouly rotating from (( 6) h) to 6. Alo the piecewie-linear holding angle ( ) a a function of the MI are hown a from (16) to (18) MI MI (16) h h

6 486 Journal of Power Electronic, Vol. 9, No., May 2009 V ` V r Re 2/Vdc α h f 2 1/Vdc f f 4 Speed reference Flux reference r r e dr e dr Speed controller ( PI controller ) Flux controller ( PI controller ) e i q e i d e i q e i d Q-current controller ( PI controller ) d-current controller ( PI controller ) V q V d NPC type three-level inverter SVPWM ia ic abc to dq r IM α h f 1 Feed-forword EMF -α h 6 A B C D e Flux Etimation i d i q r Im 0 -α h 6 6 +α 6 h 2 -α h 2 θ=ωt Fig. 6. Trajectory of reference voltage vector and phae voltage waveform in over-modulation region I I. Fig. 8. Schematic diagram of indirect vector control of induction motor. Re ` 2/ Im V r V α h 6 -α h V r V α` p α p θ` 1/ Fig. 7. Angular diplacement of reference and actual voltage Vector MI MI (17) h MI MI (18) h. Simulation Reult The validity of the propoed algorithm i verified through the imulation for the three-level inverter with induction motor. The indirect vector control method utilize the motor velocity feedback and a feed-forward lip reference to provide the intantaneou torque control. A chematic diagram of indirect vector control of the induction motor with PI controller i hown in Fig. 8. The feed-forward EMF block in current controlled VSI i required to produce the appropriated tator voltage, and the flux reference block 0 Fig. 9. Repone of current controller under repeated motor peed change between 500rpm and 1000rpm for; flux component, torque component. i included to increae the repone peed beyond the nominal peed [1]-[15]. The imulation reult of indirect vector control are hown in Fig. 9 and 10. Figure 9 how the repone of the current controller for flux component current and torque component current when the reference motor peed change from 500rpm to 1000rpm frequently. A the peed reference value change, the torque component current i regulated to generate the poitive and negative value in acceleration and deceleration region. The flux component current i alo well regulated to follow the reference value without any change under the peed change condition. Figure 10 how the magnitude and phae of reference voltage vector in tationary reference frame during the tranient tate of motor peed change. They change in linear relation to the peed change. The imulation reult of operation for the three-level

7 SVPWM Overmodulation Scheme of Three-Level Inverter for 487 Vd_ref Fig. 1. Simulation reult at MI=0.96; line to line voltage and phae current. Vq_ref (c) Fig. 10. Voltage reference of NPC type three-level inverter; magnitude of voltage reference in tationary frame, angle of that, (c) dq component of voltage vector in tationary frame. Fig. 14. Simulation reult at MI=0.974; line to line voltage and phae current. Fig. 11. Simulation reult at MI=0.69; line to line voltage and phae current. Fig. 15. Simulation reult at MI=1; line to line voltage and phae current. Fig. 12. Simulation reult at MI=0.767; line to line voltage and phae current. inverter following each region are hown in from Fig. 11 to 15. Thee figure how the reult of phae current and line-to-line voltage waveform when MI i 0.69 (Fig. 11) in the linear region mode I, (Fig. 12) in the linear region mode II, 0.96 (Fig. 1) in the over-modulation region I, and (Fig. 14) and 1 (Fig. 15) in the over-modulation region II, repectively. In Fig. 11, the line-to-line voltage ha the ame characteritic a that of two-level inverter. In Fig. 12, the line-to-line voltage ha 5

8 488 Journal of Power Electronic, Vol. 9, No., May 2009 tep o the harmonic level i much le than that of the two-level inverter. In Fig. 1, a an example of overmodulation region I, one of two ector of 2 and 4 i elected a a mall ector for the large ector A. A hown in Fig. 15, it i operated a a ix-tep mode at MI=1, and then the holding angle of each mall ector i 6. Table 4 Induction motor rating and parameter Rating Parameter pecification Power 0.75[kW] tator reitance, R.5 [Ω] Fig. 16. Picture of experiment ytem. Pole number 4 rotor reitance, R r Y voltage 80/220[V] Stator leakage inductance, L Y current 2.2/.8[A] rotor leakage inductance, L r [Ω] 1. [mh] 1. [mh] Ide_ref [2A/div] peed 1680[rpm] mutual inductance, L m [mh] frequency 60[Hz] Inertia of wheel, J e 0.002[Kgm 2] Iqe [2A/div] rpm_ref [500rpm/div] 4. Experimental Reult A digital ignal proceor (DSP) TMS20VC i ued a a control board. The rate and parameter of the induction motor ued for experiment are hown at Table IV and Table V. Figure 16 how the front view of the experimental ytem. For the pilot load of traction drive, a large flywheel ytem driving with four induction motor i ued in the experiment. The experimental reult are hown in Fig. 17 to 18 at the ame condition ued in imulation. Figure 17 how the repone of current controller with the current waveform of flux component and torque component when the reference motor peed change from 500rpm to 1000rpm or vice vera. A the peed reference value change, the flux current component are well regulated to follow the reference value. Alo, the torque current component i regulated to generate the poitive and negative value a the change of acceleration and deceleration region. Figure 18 how magnitude and angle of voltage reference vector when the reference of motor peed change. Alo it how flux component and torque component of voltage reference vector. The flux component and torque component of the voltage reference vector in the tationary frame i orthogonal for 2 alway. rpm [500rpm/div] 500m/div Fig. 17. Experimental reult; (top) flux component, (middle) torque current component, (bottom) peed. Vmag [50V/div] Θinv [5rad/div] Vq_ref [100V/div] Vd_ref [100V/div] 100m/div Fig. 18. Experimental reult; (top) voltage magnitude, (middle) phae angle, (bottom) dq component of voltage vector in tationary frame. The experimental reult of operation for three-level inverter following each region are hown in Fig. 19 to 2. Condition of each operation region are given in Table 5. The line to line voltage are meaured by a differential probe (100:1) and the phae current are done by current probe (1A:20mV). Figure 19 how the reult of phae current and line-to-line voltage when MI i 0.69 in the linear region mode I. The line-to-line voltage ha the ame characteritic a that of two-level inverter and mall ector i covered only

9 SVPWM Overmodulation Scheme of Three-Level Inverter for 489 Table 5 Operation of three-level inverter following modulation index rpm V dc V mag MI Region Liner regionⅠ Liner regionⅡ Over-modulation regionⅠ Over-modulation regionⅡ Six-tep operation Korea Science & Engineering Foundation and upported by the Minitry of Education, Science Technology (MEST) and Korea Indutrial Technology Foundation (KOTEF) through the Human Reource Training Project for Regional Innovation. Vab [200V/div] Ia [5A/div] by 1 for large ector. Fig. 20 how the reult of phae current and line-to-line voltage when MI i in the linear region mode II. The line-to-line voltage ha 5 tep o the harmonic level i much le than that of two-level inverter. Fig. 21 how the reult of phae current and line-to-line voltage when MI i 0.96 in the over-modulation region I. Figure 22 and 2 how the reult of phae current and line-to-line voltage when MI i and 1 in the over-modulation region II. Holding angle h i increaed when the modulation index i increaed at thi region. The region of MI=1 i an operated ix-tep mode. And holding angle of each mall ector i 6. Wrpm [1000rpm/div] 20m/div Fig. 19. Experimental reult at MI=0.69; (top) line to line voltage, (middle) phae current, (bottom) peed. Vab [200V/div] Ia [5A/div] Wrpm [1000rpm/div] 10m/div Fig. 20. Experimental reult at MI=0.767; (top) line to line voltage, (middle) phae current, (bottom) peed. Vab [200V/div] 5. Concluion In thi paper, a PI controller for indirect vector control of an induction motor and SVPWM technique for an NPC type -level inverter from linear region to ix-tep operation wa propoed. With thi propoed over-modulation trategy, the output voltage of the three-level inverter can be controlled in an extended range from MI=0.907 to the unit. The propoed algorithm wa verified through imulation and experimental reult with the phae current and line-to-line voltage waveform a the typical value of the modulation index from the linear region to the over-modulation region. Alo, it wa imulated with the three-level inverter fed induction motor drive and well verified with regulation performance under the dc-link voltage change and peed change condition. Ia [5A/div] Wrpm [1000rpm/div] 10m/div Fig. 21. Experimental reult at MI=0.96; (top) line to line voltage, (middle) phae current, (bottom) peed. Vab [200V/div] Ia [5A/div] Wrpm [1000rpm/div] Fig. 22. Vab [200V/div] Ia [5A/div] 10m/div Experimental reult at MI=0.974; (top) line to line voltage, (middle) phae current, (bottom) peed. Acknowledgment Thi reearch wa upported in part by grant R from the Baic Reearch Program of the Wrpm [1000rpm/div] 10m/div Fig. 2. Experimental reult at MI=1; (top) line to line voltage, (middle) phae current, (bottom) peed.

10 490 Journal of Power Electronic, Vol. 9, No., May 2009 Reference [1] J. Holtz, W. Lotzkat, and A. M. Khambadkone, On continuou control of PWM inverter in the overmodulation range including the ix-tep mode, IEEE Tran. Power Electron., Vol. 8, No. 4, pp , 199. [2] D. Lee and G. Lee, A Novel Overmodulation technique for pace-vector PWM inverter, IEEE Tran. Power Electron., Vol. 1, No. 6, pp , [] A. Nabae, I. Takahahi, and H. Akagi, A new neutral point clamped PWM inverter, IEEE Tran. Ind. Appl., IA-17,(5), pp , [4] A. Horie, S. Saito, S. Ito, T. Takaaki, and H. Ozawa Development of a three-level converter-inverter ytem with IGBT' for AC electric car, in Conf. Rec. IEE Japan IAS Annu. Meet. Rec., pp.75-78, [5] E. Akagawa, S. Kawamoto, S. Tamai, H. Okayama, and T. Uemura, Three-level PWM converter-inverter ytem for next-generation Shinkanen, in Conf. Rec. IEE Japan IAS Annu. Meet. Rec., pp.81-82, [6] C. Ma, T. Kim, D. Kang, and D. Hyun, A imple control trategy for balancing the DC-link voltage of neutralpoint-clamped inverter at low modulation index, Journal of Power Electronic, Vol., No. 4, pp , 200. [7] W. Oh, S. Han, S. Choi, G. Moon, A three phae three-level PWM witched voltage ource inverter with zero neutral point potentional, Journal of Power Electronic, Vol. 5, No., pp , [8] S. K. Mondal, J. O. P. Pinto, and B. K. Boe, A neural-network-baed pace-vector PWM controller for a three-level voltage-fed inverter induction motor drive, IEEE Tran. Ind. Appl., Vol. 8, No., pp , [9] S. K. Modal, B. K. Boe, V. Olechuk, and J. O. P. Pinto, Space vector pule width modulation of three-level inverter extending operation into overmodulation region, in Conf. Rec. IEEE PESC 02, Vol. 2, pp , [10] S. Jin, Y. Zhong, and W. Cheng, Novel SVPWM overmodulation cheme and it application in three-level inverter, in Conf. Rec. IEEE PESC 06, pp.1-6, [11] S. Venugopal and G. Narayanan, An overmodulation cheme for vector controlled induction motor drive, in Conf. Rec. IEEE PEDS 06, pp. 1-6, [12] J. Lee, J. Choi, and Y. Nihida, Overmodulation trategy of NPC type -level inverter for traction drive, in Conf. Rec. ICPE 07, pp , [1] Rowan, T.M., Kerkman, R.J. and Leggate, D, A imple on-line adaption for indirect field orientation of an induction machine, IEEE Tran. Indutry Application. Vol.27, Iue 4, pp , [14] Bimal K. Boe, Modern Power Electronic and AC Driver, pp.68-87, Prentice-Hall, Inc., [15] D. Grahame Holme and Thoma A. Lipo, Pule width modulation for power converter, pp , A John wiley & Son, Inc., 200. Kyoung-Min Kwon received hi B.S. degree in Electrical Engineering from Chungbuk National Univerity in Cheongju, Korea in 2006, where he i currently working toward hi M.S. degree. He wa a Junior Reearch Engineer at the Controller R&D Center in Woojin Indutrial Sytem from 2006 to Hi reearch interet are in ac motor drive with power converter/inverter ytem, wind power generation ytem and energy torage ytem. Jae-Moon Lee received hi B.S. and M.S. degree in Electrical Engineering from Chungbuk National Univerity in Cheongju, Korea in 2006 and 2008, repectively. He ha been an Aociate Reearch Engineer at the Drive Reearch Team Automation R&D Center in LS Indutrial Sytem ince Hi reearch interet are in AC machine drive, Power Electronic and Power ytem. Jin-Mok Lee received hi B.S. and M.S. degree in Electrical Engineering from Chungbuk National Univerity in Cheongju, Korea in 2002 and 2004, repectively, where he i currently working toward hi PhD. Hi reearch interet are in power quality analyi and controller deign of power converter and inverter ytem. Jaeho Choi received hi B.S., M.S., and Ph. D in Electrical Engineering from Seoul National Univerity, Seoul, Korea in 1979, 1981, and 1989, repectively. From 1981 to 198, he wa with Jungkyoung Technical College, Daejeon, Korea, a a Full-time Lecturer. Since 198, he ha been with the School of Electrical and Computer Engineering, Chungbuk National Univerity in Cheongju, Korea, where he i currently a profeor. In 199, 1998 and 200, he wa a viiting profeor at the Univerity of Toronto, Canada, each for one year and he wa a Danfo Viiting Profeor at Aalborg Univerity in Denmark in Hi reearch area include power electronic, power quality problem and olution, energy torage ytem, and renewable energy and microgrid ytem. He i an active member of KIEE, KIPE, and IEEE, and currently the Editor-in-Chief of JPE.

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