Low Cost CMOS, High Speed, Rail-to-Rail Amplifiers

Transcription

1 Data Sheet Low Cost CMOS, High Speed, Rail-to-Rail Amplifiers ADA89-/ADA89-/ADA89-/ADA89- FEATURES Qualified for automotive applications (ADA89-W, ADA89-W only) High speed and fast settling db bandwidth: MHz () Slew rate: 7 V/µs Settling time to.%: 8 ns Video specifications (, RL = 5 Ω). db gain flatness: 5 MHz Differential gain error:.5% Differential phase error:.5 Single-supply operation Wide supply range:.7 V to 5.5 V Output swings to within 5 mv of supply rails Low distortion: 79 dbc SFDR at MHz Linear output current: 5 ma at dbc Low power:. ma per amplifier APPLICATIONS Automotive infotainment systems Automotive driver assistance systems Imaging Consumer video Active filters Coaxial cable drivers Clock buffers Photodiode preamp Contact image sensor and buffers GENERAL DESCRIPTION The ADA89- (single), ADA89- (dual), ADA89- (triple), and ADA89- (quad) are CMOS, high speed amplifiers that offer high performance at a low cost. The amplifiers feature true single-supply capability, with an input voltage range that extends mv below the negative rail. In spite of their low cost, the ADA89 family provides high performance and versatility. The rail-to-rail output stage enables the output to swing to within 5 mv of each rail, enabling maximum dynamic range. The ADA89 family of amplifiers is ideal for imaging applications, such as consumer video, CCD buffers, and contact image sensor and buffers. Low distortion and fast settling time also make them ideal for active filter applications. The ADA89-/ADA89-/ADA89-/ADA89- are available in a wide variety of packages. The ADA89- is available in 8-lead SOIC and 5-lead SOT- packages. The ADA89- is available in 8-lead SOIC and 8-lead MSOP packages. The ADA89- and ADA89- are available in -lead SOIC and Rev. D Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. Specifications subject to change without notice. No license is granted by implication or otherwise under any patent or patent rights of Analog Devices. Trademarks and registered trademarks are the property of their respective owners. CONNECTION DIAGRAMS NC IN +IN V S ADA89- NC = NO CONNECT 8 NC 7 +V S 6 OUT 5 NC Figure. 8-Lead SOIC_N (R-8) OUT V S +IN ADA89- One Technology Way, P.O. Box 96, Norwood, MA 6-96, U.S.A. Tel: Fax: Analog Devices, Inc. All rights reserved. 5 +V S IN Figure. 5-Lead SOT- (RJ-5) OUT IN +IN V S ADA89- NC = NO CONNECT 8 +V S 7 OUT 6 IN 5 +IN Figure. 8-Lead SOIC_N (R-8) and 8-Lead MSOP (RM-8) ADA89- PD OUT PD IN PD +IN +V S V S +IN 5 +IN IN 6 9 IN OUT 7 8 OUT Figure. -Lead SOIC_N (R-) and -Lead TSSOP (RU-) ADA89- OUT IN +IN +V S +IN 5 IN 6 OUT OUT IN +IN V S +IN 9 IN 8 OUT Figure 5. -Lead SOIC_N (R-) and -Lead TSSOP (RU-) -lead TSSOP packages. The amplifiers are specified to operate over the extended temperature range of C to +5 C

2 ADA89-/ADA89-/ADA89-/ADA89- Data Sheet TABLE OF CONTENTS Features... Applications... General Description... Connection Diagrams... Revision History... Specifications... 5 V Operation... V Operation... Absolute Maximum Ratings... 6 Maximum Power Dissipation... 6 ESD Caution... 6 Typical Performance Characteristics... 7 Applications Information... 5 Using the ADA Wideband, Noninverting Gain Operation... 5 Wideband, Inverting Gain Operation... 5 Recommended Values... 5 Effect of RF on. db Gain Flatness... 6 Driving Capacitive Loads... 7 Terminating Unused Amplifiers... 8 Disable Feature (ADA89- Only)... 8 Single-Supply Operation... 8 Video Reconstruction Filter... 9 Multiplexer... 9 Layout, Grounding, and Bypassing... Power Supply Bypassing... Grounding... Input and Output Capacitance... Input-to-Output Coupling... Leakage Currents... Outline Dimensions... Ordering Guide... Automotive Products... REVISION HISTORY / Rev. C to Rev. D Added ADA89-W and ADA89-W... Universal Changes to Features Section and Applications Section... Changes to Input Offset Voltage, Input Bias Current, and Open- Loop Gain Parameters, Table... Changes to Input Offset Voltage, Input Bias Current, and Open- Loop Gain Parameters, Table... 5 Changes to Ordering Guide... Added Automotive Products Section... 9/ Rev. B to Rev. C Changes to Figure and Figure / Rev. A to Rev. B Added ADA89- and ADA Universal Added -Lead SOIC and -Lead TSSOP Packages... Universal Deleted Figure ; Renumbered Figures Sequentially... Changes to Features Section and General Description Section. Added Figure and Figure 5... Changes to Table... Changes to Table... Changes to Maximum Power Dissipation Section and Figure Added Table ; Renumbered Tables Sequentially... 6 Deleted Figure... 6 Changes to Typical Performance Characteristics Section... 7 Deleted Figure... 7 Changes to Wideband, Noninverting Gain Operation Section, Wideband, Inverting Gain Operation Section, and Table Added Table Changes to Figure Added Figure Changed Layout of Driving Capacitive Loads Section... 7 Added Disable Feature (ADA89- Only) Section and Single-Supply Operation Section... 8 Added Multiplexer Section... 9 Updated Outline Dimensions... Changes to Ordering Guide... 6/ Rev. to Rev. A Changes to Figure Changes to Figure and Figure... Updated Outline Dimensions... 8 Changes to Ordering Guide... 8 / Revision : Initial Version Rev. D Page of

3 Data Sheet ADA89-/ADA89-/ADA89-/ADA89- SPECIFICATIONS 5 V OPERATION TA = 5 C, VS = 5 V, R L = kω to.5 V, unless otherwise noted. All specifications are for the ADA89-, ADA89-, ADA89-, and ADA89-, unless otherwise noted. For the ADA89- and ADA89-, RF = 6 Ω; for the ADA89- and ADA89-, RF = 5 Ω, unless otherwise noted. Table. Parameter Test Conditions/Comments Min Typ Max Unit DYNAMIC PERFORMANCE db Small-Signal Bandwidth ADA89-/ADA89-,, VO =. V p-p MHz ADA89-/ADA89-,, VO =. V p-p MHz ADA89-/ADA89-,, VO =. V p-p, 9 MHz RL = 5 Ω to.5 V ADA89-/ADA89-,, VO =. V p-p, 96 MHz RL = 5 Ω to.5 V Bandwidth for. db Gain Flatness ADA89-/ADA89-,, VO = V p-p, 5 MHz RL = 5 Ω to.5 V, RF = 6 Ω ADA89-/ADA89-,, VO = V p-p, 5 MHz RL = 5 Ω to.5 V, RF = 7 Ω Slew Rate, tr/tf, VO = V step, % to 9% 7/ V/µs db Large-Signal Frequency Response, VO = V p-p, RL = 5 Ω MHz Settling Time to.%, VO = V step 8 ns NOISE/DISTORTION PERFORMANCE Harmonic Distortion, HD/HD fc = MHz, VO = V p-p, 79/ 9 dbc fc = MHz, VO = V p-p, G = 75/ 9 dbc Input Voltage Noise f = MHz 9 nv/ Hz Differential Gain Error (NTSC), RL = 5 Ω to.5 V.5 % Differential Phase Error (NTSC), RL = 5 Ω to.5 V.5 Degrees All-Hostile Crosstalk f = 5 MHz,, VO = V p-p 8 db DC PERFORMANCE Input Offset Voltage ±.5 ± mv ADA89-W/ADA89-W only, TMIN to TMAX ±. ±6 mv TMIN to TMAX ±. mv Offset Drift 6 µv/ C Input Bias Current pa ADA89-W/ADA89-W only, TMIN to TMAX 5 +5 na Open-Loop Gain RL = kω to.5 V 77 8 db ADA89-W/ADA89-W only, TMIN to TMAX, 66 db RL = kω to.5 V RL = 5 Ω to.5 V 7 db INPUT CHARACTERISTICS Input Resistance 5 GΩ Input Capacitance. pf Input Common-Mode Voltage Range VS. to V +VS.8 Common-Mode Rejection Ratio (CMRR) VCM = V to. V 88 db OUTPUT CHARACTERISTICS Output Voltage Swing RL = kω to.5 V. to.98 V RL = 5 Ω to.5 V.8 to.9 V Output Current % THD with MHz, VO = V p-p 5 ma Short-Circuit Current Sourcing 5 ma Sinking 7 ma Rev. D Page of

4 ADA89-/ADA89-/ADA89-/ADA89- Data Sheet Parameter Test Conditions/Comments Min Typ Max Unit POWER-DOWN PINS (PD, PD, PD) ADA89- only Threshold Voltage, VTH. V Bias Current Part enabled 65 na Part powered down µa Turn-On Time Part enabled, output rises to 9% of final value 66 ns Turn-Off Time Part powered down, output falls to % of final 9 ns value POWER SUPPLY Operating Range V Quiescent Current per Amplifier. ma Supply Current When Powered Down ADA89- only.8 ma Power Supply Rejection Ratio (PSRR) Positive PSRR +VS = 5 V to 5.5 V, VS = V 65 db Negative PSRR +VS = 5 V, VS =.5 V to V 6 db OPERATING TEMPERATURE RANGE +5 C V OPERATION TA = 5 C, VS = V, R L = kω to.5 V, unless otherwise noted. All specifications are for the ADA89-, ADA89-, ADA89-, and ADA89-, unless otherwise noted. For the ADA89- and ADA89-, RF = 6 Ω; for the ADA89- and ADA89-, RF = 5 Ω, unless otherwise noted. Table. Parameter Test Conditions/Comments Min Typ Max Unit DYNAMIC PERFORMANCE db Small-Signal Bandwidth ADA89-/ADA89-,, VO =. V p-p 9 MHz ADA89-/ADA89-,, VO =. V p-p 75 MHz ADA89-/ADA89-,, VO =. V p-p, 75 MHz RL = 5 Ω to.5 V ADA89-/ADA89-,, VO =. V p-p, 8 MHz RL = 5 Ω to.5 V Bandwidth for. db Gain Flatness ADA89-/ADA89-,, VO = V p-p, 8 MHz RL = 5 Ω to.5 V, RF = 6 Ω ADA89-/ADA89-,, VO = V p-p, 8 MHz RL = 5 Ω to.5 V, RF = 7 Ω Slew Rate, tr/tf, VO = V step, % to 9% / V/µs db Large-Signal Frequency Response, VO = V p-p, RL = 5 Ω MHz Settling Time to.%, VO = V step ns NOISE/DISTORTION PERFORMANCE Harmonic Distortion, HD/HD fc = MHz, VO = V p-p, G = 7/ 89 dbc Input Voltage Noise f = MHz 9 nv/ Hz Differential Gain Error (NTSC), RL = 5 Ω to.5 V, +VS = V, VS = V. % Differential Phase Error (NTSC), RL = 5 Ω to.5 V, +VS = V, VS = V.77 Degrees All-Hostile Crosstalk f = 5 MHz, 8 db DC PERFORMANCE Input Offset Voltage ±.5 ± mv ADA89-W/ADA89-W only, TMIN to TMAX ±. ±6 mv TMIN to TMAX ±. mv Offset Drift 6 µv/ C Input Bias Current pa ADA89-W/ADA89-W only, TMIN to TMAX 5 +5 na Rev. D Page of

5 Data Sheet ADA89-/ADA89-/ADA89-/ADA89- Parameter Test Conditions/Comments Min Typ Max Unit Open-Loop Gain RL = kω to.5 V 7 76 db ADA89-W/ADA89-W only, TMIN to TMAX, 6 db RL = kω to.5 V RL = 5 Ω to.5 V 65 db INPUT CHARACTERISTICS Input Resistance 5 GΩ Input Capacitance. pf Input Common-Mode Voltage Range VS. to V +VS.8 Common-Mode Rejection Ratio (CMRR) VCM = V to.5 V 87 db OUTPUT CHARACTERISTICS Output Voltage Swing RL = kω to.5 V. to.98 V RL = 5 Ω to.5 V.7 to.87 V Output Current % THD with MHz, VO = V p-p 7 ma Short-Circuit Current Sourcing 8 ma Sinking 6 ma POWER-DOWN PINS (PD, PD, PD) ADA89- only Threshold Voltage, VTH. V Bias Current Part enabled 8 na Part powered down µa Turn-On Time Part enabled, output rises to 9% of final value 85 ns Turn-Off Time Part powered down, output falls to % of final 58 ns value POWER SUPPLY Operating Range V Quiescent Current per Amplifier.5 ma Supply Current When Powered Down ADA89- only.7 ma Power Supply Rejection Ratio (PSRR) Positive PSRR +VS = V to.5 V, VS = V 76 db Negative PSRR +VS = V, VS =.5 V to V 7 db OPERATING TEMPERATURE RANGE +5 C Rev. D Page 5 of

6 ADA89-/ADA89-/ADA89-/ADA89- Data Sheet ABSOLUTE MAXIMUM RATINGS Table. Parameter Rating Supply Voltage 6 V Input Voltage (Common Mode) VS.5 V to +VS Differential Input Voltage ±VS Storage Temperature Range 65 C to +5 C Operating Temperature Range C to +5 C Lead Temperature (Soldering, sec) C Stresses above those listed under Absolute Maximum Ratings may cause permanent damage to the device. This is a stress rating only; functional operation of the device at these or any other conditions above those indicated in the operational section of this specification is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability. MAXIMUM POWER DISSIPATION The maximum power that can be safely dissipated by the ADA89-/ADA89-/ADA89-/ADA89- is limited by the associated rise in junction temperature. The maximum safe junction temperature for plastic encapsulated devices is determined by the glass transition temperature of the plastic, approximately 5 C. Temporarily exceeding this limit can cause a shift in parametric performance due to a change in the stresses exerted on the die by the package. Exceeding a junction temperature of 75 C for an extended period can result in device failure. The still-air thermal properties of the package (θja), the ambient temperature (TA), and the total power dissipated in the package (PD) can be used to determine the junction temperature of the die. The junction temperature can be calculated as TJ = TA + (PD θja) () The power dissipated in the package (PD) is the sum of the quiescent power dissipation and the power dissipated in the package due to the load drive for all outputs. It can be calculated by PD = (VT IS) + (VS VOUT) (VOUT/RL) () where: VT is the total supply rail. IS is the quiescent current. VS is the positive supply rail. VOUT is the output of the amplifier. RL is the output load of the amplifier. To ensure proper operation, it is necessary to observe the maximum power derating curves shown in Figure 6. These curves are derived by setting TJ = 5 C in Equation. Figure 6 shows the maximum safe power dissipation in the package vs. the ambient temperature on a JEDEC standard -layer board. MAXIMUM POWER DISSIPATION (W) LEAD MSOP 5-LEAD SOT- -LEAD TSSOP -LEAD SOIC_N 8-LEAD SOIC_N AMBIENT TEMPERATURE ( C) T J = 5 C Figure 6. Maximum Power Dissipation vs. Ambient Temperature Table lists the thermal resistance (θja) for each ADA89-/ ADA89-/ADA89-/ADA89- package. Table. Package Type θja Unit 5-Lead SOT- 6 C/W 8-Lead SOIC_N 5 C/W 8-Lead MSOP C/W -Lead SOIC_N 6 C/W -Lead TSSOP 8 C/W ESD CAUTION 85- Rev. D Page 6 of

7 Data Sheet ADA89-/ADA89-/ADA89-/ADA89- TYPICAL PERFORMANCE CHARACTERISTICS Unless otherwise noted, all plots are characterized for the ADA89-, ADA89-, ADA89-, and ADA89-. For the ADA89- and ADA89-, the typical RF value is 6 Ω. For the ADA89- and ADA89-, the typical RF value is 5 Ω V OUT = mv p-p 9 R F = 6Ω R L = kω. k G = OR + G = +5 Figure 7. Small-Signal Frequency Response vs. Gain, VS = 5 V, ADA89-/ADA V OUT = mv p-p R F = 5Ω R L = kω G = +5 G = OR +. k Figure. Small-Signal Frequency Response vs. Gain, VS = 5 V, ADA89-/ADA V S =.7V 6 V S =.7V CLOSED-LOOP GAIN (db) 6 9 CLOSED-LOOP GAIN (db) 6 9 V OUT = mv p-p R L = kω 5. k Figure 8. Small-Signal Frequency Response vs. Supply Voltage, ADA89-/ADA V OUT = mv p-p R L = kω 5. k Figure. Small-Signal Frequency Response vs. Supply Voltage, ADA89-/ADA CLOSED-LOOP GAIN (db) 5 +5 C V OUT = mv p-p R L = kω. k +85 C C +5 C Figure 9. Small-Signal Frequency Response vs. Temperature, VS = 5 V, ADA89-/ADA89- C 85- CLOSED-LOOP GAIN (db) 5 V OUT = mv p-p R L = kω +5 C +85 C +5 C C C. k Figure. Small-Signal Frequency Response vs. Temperature, VS = 5 V, ADA89-/ADA Rev. D Page 7 of

8 ADA89-/ADA89-/ADA89-/ADA89- Data Sheet CLOSED-LOOP GAIN (db) C +5 C 5 V OUT = mv p-p R L = kω 6. k C +5 C C 85- CLOSED-LOOP GAIN (db) C +5 C +5 C C C 5 V OUT = mv p-p R L = kω 6. k Figure. Small-Signal Frequency Response vs. Temperature, VS = V, ADA89-/ADA89- Figure 6. Small-Signal Frequency Response vs. Temperature, VS = V, ADA89-/ADA V OUT =.V p-p. R F = 6Ω V R L = 5Ω OUT =.V p-p R F = 7Ω R L = 5Ω V OUT =.V p-p V OUT =.V p-p Figure.. db Gain Flatness vs. Supply Voltage,, ADA89-/ADA89- Figure 7.. db Gain Flatness vs. Supply Voltage,, ADA89-/ADA R F = 6Ω G = +5 R F = 6Ω 8 9 R L = 5Ω. k R F = Ω G = R F = 6Ω Figure 5. Large-Signal Frequency Response vs. Gain, VS = 5 V, ADA89-/ADA R L = 5Ω G = +5 R F = 5Ω R F = 5Ω G = R F = 5Ω R F = Ω. k Figure 8. Large-Signal Frequency Response vs. Gain, VS = 5 V, ADA89-/ADA Rev. D Page 8 of

9 Data Sheet ADA89-/ADA89-/ADA89-/ADA R F = 6Ω R L = 5Ω G = V OUT = V p-p G = +5. k Figure 9. Large-Signal Frequency Response vs. Gain, VS = V, ADA89-/ADA R F = 5Ω R L = 5Ω G = +5 G = V OUT = V p-p. k Figure. Large-Signal Frequency Response vs. Gain, VS = V, ADA89-/ADA DISTORTION (dbc) R L = kω SECOND HARMONIC THIRD HARMONIC THIRD HARMONIC. SECOND HARMONIC Figure. Harmonic Distortion (HD, HD) vs. Frequency, VS = 5 V 85-8 DISTORTION (dbc) R L = kω SECOND HARMONIC SECOND HARMONIC THIRD HARMONIC OUT 8 IN kω 5Ω V S =.V THIRD HARMONIC CONFIGURATION 9. +V S = +.9V Figure. Harmonic Distortion (HD, HD) vs. Frequency, VS = V 85-9 DISTORTION (dbc) R F = 6Ω R L = kω f C = MHz G = SECOND HARMONIC THIRD HARMONIC OUTPUT VOLTAGE (V p-p) SECOND HARMONIC G = THIRD HARMONIC Figure. Harmonic Distortion (HD, HD) vs. Output Voltage, VS = 5 V 85- DISTORTION (dbc) V S = +.9V IN 5Ω V S =.V G = SECOND HARMONIC CONFIGURATION SECOND HARMONIC OUT kω THIRD HARMONIC OUTPUT VOLTAGE (V p-p) G = THIRD HARMONIC f C = MHz Figure. Harmonic Distortion (HD, HD) vs. Output Voltage, VS = V 85- Rev. D Page 9 of

10 ADA89-/ADA89-/ADA89-/ADA89- Data Sheet 5 R F = 6Ω R L = 5Ω f C = MHz SECOND HARMONIC THIRD HARMONIC k DISTORTION (dbc) SECOND HARMONIC THIRD HARMONIC VOLTAGE NOISE (nv/ Hz) OUTPUT VOLTAGE (V p-p) Figure 5. Harmonic Distortion (HD, HD) vs. Output Voltage, 85- k k k M M FREQUENCY (Hz) Figure 8. Input Voltage Noise vs. Frequency 85-5 OPEN-LOOP GAIN (db) PHASE GAIN k R L = kω Figure 6. Open-Loop Gain and Phase vs. Frequency PHASE (Degrees) 85- DIFFERENTIAL GAIN ERROR (%) DIFFERENTIAL PHASE ERROR (Degrees) , R F = 6Ω, R L = 5Ω ST ND RD TH 5 TH 6 TH 7 TH 8 TH 9 TH TH, R F = 6Ω, R L = 5Ω ST ND RD TH 5 TH 6 TH 7 TH 8 TH 9 TH TH MODULATING RAMP LEVEL (IRE) Figure 9. Differential Gain and Phase Errors R L = 5Ω V OUT = mv p-p. k C L = 7pF C L = pf C L = pf C L = pf 6 5 R L = 5Ω V OUT = mv p-p C L = 7pF C L = pf C L = pf C L = pf Figure 7. Small-Signal Frequency Response vs. CL, ADA89-/ADA k Figure. Small-Signal Frequency Response vs. CL, ADA89-/ADA Rev. D Page of

11 Data Sheet ADA89-/ADA89-/ADA89-/ADA89- k OUTPUT IMPEDANCE (Ω).... Figure. Closed-Loop Output Impedance vs. Frequency, Part Enabled 85-6 OUTPUT IMPEDANCE (Ω) k k.. Figure. Closed-Loop Output Impedance vs. Frequency, Part Disabled (ADA89- Only) OUTPUT VOLTAGE (mv) V OUT = mv p-p R L = kω OUTPUT VOLTAGE (V) R L = kω R L = 5Ω R L = kω R L = 5Ω 5mV/DIV Figure. Small-Signal Step Response, 5ns/DIV TIME (ns) Figure 5. Large-Signal Step Response, 85-7 R L = kω.5 R L = kω V OUT = V p-p OUTPUT VOLTAGE (V) R L = 5Ω OUTPUT VOLTAGE (V) R L = 5Ω.5.5V/DIV 5ns/DIV V/DIV 5ns/DIV 85-5 Figure. Large-Signal Step Response, VS = 5 V, Figure 6. Large-Signal Step Response, VS = V, Rev. D Page of

12 ADA89-/ADA89-/ADA89-/ADA89- Data Sheet SETTLING (%).... V S =5V G=+ R L = 5Ω V OUT =Vp-p SLEW RATE (V/µs) R L = 5Ω FALLING EDGE RISING EDGE TIME (ns) Figure 7. Short-Term Settling Time to.% OUTPUT STEP (V) Figure. Slew Rate vs. Output Step 85-5 INPUT V S = ±.5V R L = kω V S = ±.5V R L = kω OUTPUT INPUT AMPLITUDE (V) AMPLITUDE (V) OUTPUT V/DIV 5ns/DIV Figure 8. Input Overdrive Recovery from Positive Rail 85-7 V/DIV 5ns/DIV Figure. Input Overdrive Recovery from Negative Rail 85-6 OUTPUT V S = ±.5V G = R L = kω INPUT V S = ±.5V G = R L = kω AMPLITUDE (V) INPUT AMPLITUDE (V) V/DIV 5ns/DIV 85-7 OUTPUT V/DIV 5ns/DIV 85-5 Figure 9. Output Overdrive Recovery from Positive Rail Figure. Output Overdrive Recovery from Negative Rail Rev. D Page of

13 Data Sheet ADA89-/ADA89-/ADA89-/ADA89- CMRR (db) ISOLATION (db) R L = 5Ω TSSOP SOIC 9.. Figure. CMRR vs. Frequency k Figure 6. Forward Isolation vs. Frequency (ADA89- Only) 85-8 PSRR (db) Vs = 5V +PSRR PSRR OUTPUT SATURATION VOLTAGE (V) G = R F = 6Ω V OH, +5 C V OH, +5 C V OH, C V OL, +5 C V OL, +5 C V OL, C 8.. Figure. PSRR vs. Frequency I LOAD (ma) Figure 7. Output Saturation Voltage vs. Load Current and Temperature CROSSTALK (db) Vs = 5V R L = kω QUIESCENT SUPPLY CURRENT (ma) k Figure 5. All-Hostile Crosstalk (Output-to-Output) vs. Frequency TEMPERATURE (ºC) Figure 8. Supply Current per Amplifier vs. Temperature Rev. D Page of

14 ADA89-/ADA89-/ADA89-/ADA89- Data Sheet. QUIESCENT SUPPLY CURRENT (ma) SUPPLY VOLTAGE (V) Figure 9. Supply Current per Amplifier vs. Supply Voltage Rev. D Page of

15 Data Sheet APPLICATIONS INFORMATION USING THE ADA89 ADA89-/ADA89-/ADA89-/ADA89- WIDEBAND, INVERTING GAIN OPERATION Understanding the subtleties of the ADA89 family of amplifiers provides insight into how to extract the peak performance from the device. The following sections describe the effect of gain, component values, and parasitics on the performance of the ADA89. The wideband, noninverting gain configuration of the ADA89 is shown in Figure 5; the wideband, inverting gain configuration of the ADA89 is shown in Figure 5. WIDEBAND, NONINVERTING GAIN OPERATION 5Ω SOURCE V I R T R G +V S.µF ADA89 R F V O µf R L +V S.µF µf 5Ω SOURCE V I.µF µf VO R T ADA89 R F R L V S Figure 5. Inverting Gain Configuration Figure 5 shows the inverting gain configuration. For the inverting gain configuration, set the parallel combination of RT and RG to match the input source impedance. 85- R G V S.µF µf 85- Note that a bias current cancellation resistor is not required in the noninverting input of the amplifier because the input bias current of the ADA89 is very low (less than pa). Therefore, the dc errors caused by the bias current are negligible. Figure 5. Noninverting Gain Configuration In Figure 5, RF and RG denote the feedback and gain resistors, respectively. Together, RF and RG determine the noise gain of the amplifier. The value of RF defines the. db bandwidth (for more information, see the Effect of RF on. db Gain Flatness section). Typical RF values range from 59 Ω to 698 Ω for the ADA89-/ADA89-. Typical RF values range from Ω to 5 Ω for the ADA89-/ADA89-. In a controlled impedance signal path, RT is used as the input termination resistor designed to match the input source impedance. Note that RT is not required for normal operation. RT is generally set to match the input source impedance. For both noninverting and inverting gain configurations, it is often useful to increase the RF value to decrease the load on the output. Increasing the RF value improves harmonic distortion at the expense of reducing the. db bandwidth of the amplifier. This effect is discussed further in the Effect of RF on. db Gain Flatness section. RECOMMENDED VALUES Table 5 and Table 6 provide a quick reference for various configurations and show the effect of gain on the db small-signal bandwidth, slew rate, and peaking of the ADA89-/ADA89-/ ADA89-/ADA89-. Note that as the gain increases, the small-signal bandwidth decreases, as is expected from the gain bandwidth product relationship. In addition, the phase margin improves with higher gains, and the amplifier becomes more stable. As a result, the peaking in the frequency response is reduced (see Figure 7 and Figure ). Table 5. Recommended Component Values and Effect of Gain on ADA89-/ADA89- Performance (RL = kω) Feedback Network Values db Small-Signal Bandwidth (MHz) Slew Rate (V/µs) Gain RF (Ω) RG (Ω) VOUT = mv p-p tr tf Peaking (db) Open Rev. D Page 5 of

16 ADA89-/ADA89-/ADA89-/ADA89- Data Sheet Table 6. Recommended Component Values and Effect of Gain on ADA89-/ADA89- Performance (RL = kω) Feedback Network Values db Small-Signal Bandwidth (MHz) Slew Rate (V/µs) Gain RF (Ω) RG (Ω) VOUT = mv p-p tr tf Peaking (db) Open EFFECT OF R F ON. db GAIN FLATNESS Gain flatness is an important specification in video applications. It represents the maximum allowable deviation in the signal amplitude within the pass band. Tests have revealed that the human eye is unable to distinguish brightness variations of less than %, which translates into a. db signal drop within the pass band or, put simply,. db gain flatness. The PCB layout configuration and bond pads of the chip often contribute to stray capacitance. The stray capacitance at the inverting input forms a pole with the feedback and gain resistors. This additional pole adds phase shift and reduces phase margin in the closed-loop phase response, causing instability in the amplifier and peaking in the frequency response. Figure 5 and Figure 5 show the effect of using various values for Feedback Resistor RF on the. db gain flatness of the parts. Figure 5 shows the effect for the ADA89-/ADA89-. Figure 5 show the effect for the ADA89-/ADA89-. Note that a larger RF value causes more peaking because the additional pole formed by RF and the input stray capacitance shifts down in frequency and interacts significantly with the internal poles of the amplifier..... R G = R F = 698Ω R G = R F = 6Ω R G = R F = 59Ω. R L = 5Ω.. R G = R F = 69Ω Figure 5.. db Gain Flatness, Noninverting Gain Configuration, ADA89-/ADA R G = R F = 5Ω R G = R F = Ω R G = R F = 57Ω R G = R F = Ω.. R L = 5Ω.5. Figure 5.. db Gain Flatness, Noninverting Gain Configuration, ADA89-/ADA89- To obtain the desired. db bandwidth, adjust the feedback resistor, RF, as shown in Figure 5 and Figure 5. If RF cannot be adjusted, a small capacitor can be placed in parallel with RF to reduce peaking. The feedback capacitor, CF, forms a zero with the feedback resistor, which cancels out the pole formed by the input stray capacitance and the gain and feedback resistors. For a first pass in determining the CF value, use the following equation: RG CS = RF CF where: RG is the gain resistor. CS is the input stray capacitance. RF is the feedback resistor. CF is the feedback capacitor. Using this equation, the original closed-loop frequency response of the amplifier is restored, as if there is no stray input capacitance. Most often, however, the value of CF is determined empirically. Figure 5 shows the effect of using various values for the feedback capacitor to reduce peaking. In this case, the ADA89-/ ADA89- are used for demonstration purposes and RF = RG = 6 Ω. The input stray capacitance, together with the board parasitics, is approximately pf Rev. D Page 6 of

17 Data Sheet ADA89-/ADA89-/ADA89-/ADA C F =.pf. R F = 6Ω R L = 5Ω.. C F = pf Figure 5.. db Gain Flatness vs. CF, VS = 5 V, ADA89-/ADA89- DRIVING CAPACITIVE LOADS C F = pf A highly capacitive load reacts with the output impedance of the amplifiers, causing a loss of phase margin and subsequent peaking or even oscillation. The ADA89-/ADA89- are used to demonstrate this effect (see Figure 55 and Figure 56). MAGNITUDE (db) OUTPUT VOLTAGE (mv) V OUT = mv p-p 8 R L = kω C L = 6.8pF. Figure 55. Closed-Loop Frequency Response, CL = 6.8 pf, ADA89-/ADA89-5mV/DIV Figure 56. mv Step Response, CL = 6.8 pf, ADA89-/ADA89- R L = kω C L = 6.8pF 5ns/DIV These four methods minimize the output capacitive loading effect. Reducing the output resistive load. This pushes the pole further away and, therefore, improves the phase margin. Increasing the phase margin with higher noise gains. As the closed-loop gain is increased, the larger phase margin allows for large capacitive loads with less peaking. Adding a parallel capacitor (CF) with RF, from IN to the output. This adds a zero in the closed-loop frequency response, which tends to cancel out the pole formed by the capacitive load and the output impedance of the amplifier. See the Effect of RF on. db Gain Flatness section for more information. Placing a small value resistor (RS) in series with the output to isolate the load capacitor from the output stage of the amplifier. Figure 57 shows the effect of using a snub resistor (RS) on reducing the peaking in the worst-case frequency response (gain of +). Using RS = Ω reduces the peaking by db, with the trade-off that the closed-loop gain is reduced by.9 db due to attenuation at the output. RS can be adjusted from Ω to Ω to maintain an acceptable level of peaking and closed-loop gain, as shown in Figure 57. MAGNITUDE (db) V OUT = mv p-p R L = kω C L = 6.8pF V IN mv STEP 5Ω R S = Ω R S = Ω. R S R L C L OUT Figure 57. Closed-Loop Frequency Response with Snub Resistor, CL = 6.8 pf Figure 58 shows that the transient response is also much improved by the snub resistor (RS = Ω) compared to that of Figure 56. OUTPUT VOLTAGE (mv) 5mV/DIV R L = kω C L = 6.8pF R S = Ω 5ns/DIV Figure 58. mv Step Response, CL = 6.8 pf, RS = Ω Rev. D Page 7 of

18 ADA89-/ADA89-/ADA89-/ADA89- Data Sheet TERMINATING UNUSED AMPLIFIERS Terminating unused amplifiers in a multiamplifier package is an important step in ensuring proper operation of the functional amplifier. Unterminated amplifiers can oscillate and draw excessive power. The recommended procedure for terminating unused amplifiers is to connect any unused amplifiers in a unity-gain configuration and to connect the noninverting input to midsupply voltage. With symmetrical bipolar power supplies, this means connecting the noninverting input to ground, as shown in Figure 59. +V S ADA89 V S Figure 59. Terminating Unused Amplifier with Symmetrical Bipolar Power Supplies In single power supply applications, a synthetic midsupply source must be created. This can be accomplished with a simple resistive voltage divider. Figure 6 shows the proper connection for terminating an unused amplifier in a single-supply configuration..5kω.5kω +V S ADA SINGLE-SUPPLY OPERATION The ADA89 can also be operated from a single power supply. Figure 6 shows the ADA89- configured as a single 5 V supply video driver. The input signal is ac-coupled into the amplifier via Capacitor C. Resistor R and Resistor R establish the input midsupply reference for the amplifier. Capacitor C5 prevents constant current from being drawn through the gain set resistor (RG) and enables the ADA89- at dc to provide unity gain to the input midsupply voltage, thereby establishing the output voltage at midsupply. Capacitor C6 is the output coupling capacitor. The large-signal frequency response obtained with singlesupply operation is identical to the bipolar supply operation (Figure 8 shows the large-signal frequency response). Four pairs of low frequency poles are formed by R/ and C, R and C, RG and C5, and RL and C6. With this configuration, the db cutoff frequency at low frequency is Hz. The values of C, C, C5, and C6 can be adjusted to change the low frequency db cutoff point to suit individual design needs. For more information about single-supply operation of op amps, see the Analog Dialogue article Avoiding Op Amp Instability Problems in Single-Supply Applications (Volume 5, Number ) at C µf +5V C µf Figure 6. Terminating Unused Amplifier with Single Power Supply DISABLE FEATURE (ADA89- ONLY) The ADA89- includes a power-down feature that can be used to save power when an amplifier is not in use. When an amplifier is powered down, its output goes to a high impedance state. The output impedance decreases as frequency increases; this effect can be observed in Figure. With the power-down function, a forward isolation of db can be achieved at 5 MHz. Figure 6 shows the forward isolation vs. frequency data. The power-down feature is asserted by pulling the PD, PD, or PD pin low V IN +5V R 5Ω R 5kΩ R kω C µf R 5kΩ R G 5Ω C5 µf R F 5Ω C.µF V S C6 µf ADA89- R L 5Ω Figure 6. Single-Supply Video Driver Schematic V OUT Table 7 summarizes the operation of the power-down feature. Table 7. Disable Function Power-Down Pin Connection (PDx) >VTH or floating <VTH Amplifier Status Enabled Disabled Rev. D Page 8 of

19 Data Sheet ADA89-/ADA89-/ADA89-/ADA89- VIDEO RECONSTRUCTION FILTER A common application for active filters is at the output of video digital-to-analog converters (DACs)/encoders. The filter, or more appropriately, the video reconstruction filter, is used at the output of a video DAC/encoder to eliminate the multiple images that are created during the sampling process within the DAC. For portable video applications, the ADA89 is an ideal choice due to its lower power requirements and high performance. For active filters, a good rule of thumb is that the db bandwidth of the amplifiers be at least times higher than the corner frequency of the filter. This ensures that no initial roll-off is introduced by the amplifier and that the pass band is flat until the cutoff frequency. An example of a 5 MHz, -pole, Sallen-Key, low-pass video reconstruction filter is shown in Figure 6. This circuit features a gain of +, a. db bandwidth of 7. MHz, and over 7 db attenuation at 9.7 MHz (see Figure 6). The filter has three poles: two poles are active, with a third passive pole (R6 and C) placed at the output. C improves the filter roll-off. R6, R7, and R8 make up the video load of 5 Ω. Components R6, C, R7, R8, and the input termination of the network analyzer form a 6 db attenuator; therefore, the reference level is roughly db, as shown in Figure 6. C 5pF MULTIPLEXER The ADA89- has a disable pin used to power down the amplifier to save power or to create a mux circuit. If two or more ADA89- outputs are connected together and only one output is enabled, then only the signal of the enabled amplifier appears at the output. This configuration is used to select from various input signal sources. Additionally, the same input signal is applied to different gain stages, or differently tuned filters, to make a gain-step amplifier or a selectable frequency amplifier. Figure 6 shows a schematic of two ADA89- devices used to create a mux that selects between two inputs. One input is a V p-p, MHz sine wave; the other input is a V p-p, MHz sine wave. V p-p MHz 9.9Ω 5Ω +.5V ADA89-.5V +.5V.µF.µF 5Ω.µF µf µf µf 9.9Ω 9.9Ω 9.9Ω V OUT V IN R R 7Ω R 5Ω C 5pF R kω +5V R6 6.8Ω R7 68.Ω C nf R8 75Ω V OUT V p-p MHz 9.9Ω ADA89-.µF.5V 5Ω µf MAGNITUDE (db) R5 kω C 5pF Figure 6. 5 MHz Video Reconstruction Filter Schematic Figure 6. Video Reconstruction Filter Frequency Performance SELECT 5Ω HCO Figure 6. Two-to-One Multiplexer Using Two ADA86- Devices The select signal and the output waveforms for this circuit are shown in Figure 65. OUTPUT SELECT V/DIV 5V/DIV Figure 65. ADA86- Mux Output µs/div µs/div Rev. D Page 9 of

20 ADA89-/ADA89-/ADA89-/ADA89- Data Sheet LAYOUT, GROUNDING, AND BYPASSING POWER SUPPLY BYPASSING Power supply pins are additional op amp inputs, and care must be taken so that a noise-free, stable dc voltage is applied. The purpose of bypass capacitors is to create a low impedance path from the supply to ground over a range of frequencies, thereby shunting or filtering the majority of the noise to ground. Bypassing is also critical for stability, frequency response, distortion, and PSRR performance. If traces are used between components and the package, chip capacitors of. μf (X7R or NPO) are critical and should be placed as close as possible to the amplifier package. The 58 case size for such a capacitor is recommended because it offers low series inductance and excellent high frequency performance. Larger chip capacitors, such as. μf capacitors, can be shared among a few closely spaced active components in the same signal path. A μf tantalum capacitor is less critical for high frequency bypassing, but it provides additional bypassing for lower frequencies. GROUNDING When possible, ground and power planes should be used. Ground and power planes reduce the resistance and inductance of the power supply feeds and ground returns. If multiple planes are used, they should be stitched together with multiple vias. The returns for the input, output terminations, bypass capacitors, and RG should all be kept as close to the ADA89 as possible. Ground vias should be placed at the side or at the very end of the component mounting pads to provide a solid ground return. The output load ground and the bypass capacitor grounds should be returned to a common point on the ground plane to minimize parasitic inductance and to help improve distortion performance. INPUT AND OUTPUT CAPACITANCE Parasitic capacitance can cause peaking and instability and, therefore, should be minimized to ensure stable operation. High speed amplifiers are sensitive to parasitic capacitance between the inputs and ground. A few picofarads of capacitance reduce the input impedance at high frequencies, in turn increasing the gain of the amplifier and causing peaking of the frequency response or even oscillations, if severe enough. It is recommended that the external passive components that are connected to the input pins be placed as close as possible to the inputs to avoid parasitic capacitance. In addition, the ground and power planes under the pins of the ADA89 should be cleared of copper to prevent parasitic capacitance between the input and output pins to ground. This is because a single mounting pad on a SOIC footprint can add as much as. pf of capacitance to ground if the ground or power plane is not cleared under the ADA89 pins. In fact, the ground and power planes should be kept at a distance of at least.5 mm from the input pins on all layers of the board. INPUT-TO-OUTPUT COUPLING To minimize capacitive coupling between the inputs and outputs and to avoid any positive feedback, the input and output signal traces should not be parallel. In addition, the input traces should not be close to each other. A minimum of 7 mils between the two inputs is recommended. LEAKAGE CURRENTS In extremely low input bias current amplifier applications, stray leakage current paths must be kept to a minimum. Any voltage differential between the amplifier inputs and nearby traces sets up a leakage path through the PCB. Consider a V signal and GΩ to ground present at the input of the amplifier. The resultant leakage current is pa; this is 5 the typical input bias current of the amplifier. Poor PCB layout, contamination, and the board material can create large leakage currents. Common contaminants on boards are skin oils, moisture, solder flux, and cleaning agents. Therefore, it is imperative that the board be thoroughly cleaned and that the board surface be free of contaminants to take full advantage of the low input bias currents of the ADA89. To significantly reduce leakage paths, a guard ring/shield should be used around the inputs. The guard ring circles the input pins and is driven to the same potential as the input signal, thereby reducing the potential difference between pins. For the guard ring to be completely effective, it must be driven by a relatively low impedance source and should completely surround the input leads on all sides, above and below, using a multilayer board (see Figure 66). GUARD RING INVERTING GUARD RING NONINVERTING Figure 66. Guard Ring Configurations The 5-lead SOT- package for the ADA89- presents a challenge in keeping the leakage paths to a minimum. The pin spacing is very tight, so extra care must be used when constructing the guard ring (see Figure 67 for the recommended guard ring construction). OUT ADA89- V S +IN +V S OUT +V S ADA89- IN V S +IN INVERTING NONINVERTING Figure 67. Guard Ring Layout, 5-Lead SOT- IN Rev. D Page of

21 Data Sheet ADA89-/ADA89-/ADA89-/ADA89- OUTLINE DIMENSIONS 5. (.968).8 (.89). (.57).8 (.97) (.) 5.8 (.8).5 (.98). (.) COPLANARITY. SEATING PLANE.7 (.5) BSC.75 (.688).5 (.5).5 (.). (.) 8.5 (.98).7 (.67).5 (.96).5 (.99).7 (.5). (.57) 5 COMPLIANT TO JEDEC STANDARDS MS--AA CONTROLLING DIMENSIONS ARE IN MILLIMETERS; INCH DIMENSIONS (IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN. Figure Lead Standard Small Outline Package [SOIC_N] Narrow Body (R-8) Dimensions shown in millimeters and (inches) 7-A BSC.95 BSC MAX.5 MIN.5 MAX.5 MIN.5 MAX.95 MIN SEATING PLANE. MAX.8 MIN 5.6 BSC COMPLIANT TO JEDEC STANDARDS MO-78-AA ---A Figure Lead Small Outline Transistor Package [SOT-] (RJ-5) Dimensions shown in millimeters Rev. D Page of

22 ADA89-/ADA89-/ADA89-/ADA89- Data Sheet PIN IDENTIFIER.65 BSC COPLANARITY...5. MAX 6 5 MAX..9 COMPLIANT TO JEDEC STANDARDS MO-87-AA Figure 7. 8-Lead Mini Small Outline Package [MSOP] (RM-8) Dimensions shown in millimeters B 8.75 (.5) 8.55 (.66). (.575).8 (.96) (.) 5.8 (.8).5 (.98). (.9) COPLANARITY..7 (.5) BSC.5 (.). (.).75 (.689).5 (.5) SEATING PLANE 8.5 (.98).7 (.67).5 (.97).5 (.98).7 (.5). (.57) 5 COMPLIANT TO JEDEC STANDARDS MS--AB CONTROLLING DIMENSIONS ARE IN MILLIMETERS; INCH DIMENSIONS (IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN. Figure 7. -Lead Standard Small Outline Package [SOIC_N] Narrow Body (R-) Dimensions shown in millimeters and (inches) 666-A BSC 7 PIN BSC.5.5. COPLANARITY.9.. MAX SEATING PLANE..9 8 COMPLIANT TO JEDEC STANDARDS MO-5-AB- Figure 7. -Lead Thin Shrink Small Outline Package [TSSOP] (RU-) Dimensions shown in millimeters A Rev. D Page of

23 Data Sheet ADA89-/ADA89-/ADA89-/ADA89- ORDERING GUIDE Model, Temperature Range Package Description Package Option Branding ADA89-ARZ C to +5 C 8-Lead SOIC_N R-8 ADA89-ARZ-RL C to +5 C 8-Lead SOIC_N, Tape and Reel R-8 ADA89-ARZ-R7 C to +5 C 8-Lead SOIC_N, 7 Tape and Reel R-8 ADA89-ARJZ-R7 C to +5 C 5-Lead SOT-, 7 Tape and Reel RJ-5 HW ADA89-ARJZ-RL C to +5 C 5-Lead SOT-, Tape and Reel RJ-5 HW ADA89-WARJZ-R7 C to +5 C 5-Lead SOT-, Tape and Reel RJ-5 HS ADA89-ARZ C to +5 C 8-Lead SOIC_N R-8 ADA89-ARZ-RL C to +5 C 8-Lead SOIC_N, Tape and Reel R-8 ADA89-ARZ-R7 C to +5 C 8-Lead SOIC_N, 7 Tape and Reel R-8 ADA89-ARMZ C to +5 C 8-Lead MSOP RM-8 HU ADA89-ARMZ-RL C to +5 C 8-Lead MSOP, " Tape and Reel RM-8 HU ADA89-ARMZ-R7 C to +5 C 8-Lead MSOP, 7" Tape and Reel RM-8 HU ADA89-WARMZ-R7 C to +5 C 8-Lead MSOP, 7" Tape and Reel RM-8 HT ADA89-ARUZ C to +5 C -Lead TSSOP RU- ADA89-ARUZ-R7 C to +5 C -Lead TSSOP, 7 Tape and Reel RU- ADA89-ARUZ-RL C to +5 C -Lead TSSOP, Tape and Reel RU- ADA89-ARZ C to +5 C -Lead SOIC_N R- ADA89-ARZ-R7 C to +5 C -Lead SOIC_N, 7 Tape and Reel R- ADA89-ARZ-RL C to +5 C -Lead SOIC_N, Tape and Reel R- ADA89-ARUZ C to +5 C -Lead TSSOP RU- ADA89-ARUZ-R7 C to +5 C -Lead TSSOP, 7 Tape and Reel RU- ADA89-ARUZ-RL C to +5 C -Lead TSSOP, Tape and Reel RU- ADA89-ARZ C to +5 C -Lead SOIC_N R- ADA89-ARZ-R7 C to +5 C -Lead SOIC_N, 7 Tape and Reel R- ADA89-ARZ-RL C to +5 C -Lead SOIC_N, Tape and Reel R- ADA89-AR-EBZ Evaluation Board for 8-Lead SOIC_N ADA89-ARJ-EBZ Evaluation Board for 5-Lead SOT- ADA89-AR-EBZ Evaluation Board for 8-Lead SOIC_N ADA89-ARM-EBZ Evaluation Board for 8-Lead MSOP ADA89-AR-EBZ Evaluation Board for -Lead SOIC_N ADA89-ARU-EBZ Evaluation Board for -Lead TSSOP ADA89-AR-EBZ Evaluation Board for -Lead SOIC_N ADA89-ARU-EBZ Evaluation Board for -Lead TSSOP Z = RoHS Compliant Part. W = Qualified for Automotive Applications. AUTOMOTIVE PRODUCTS The ADA89-W and ADA89-W models are available with controlled manufacturing to support the quality and reliability requirements of automotive applications. Note that these automotive models may have specifications that differ from the commercial models; therefore, designers should review the Specifications section of this data sheet carefully. Only the automotive grade products shown are available for use in automotive applications. Contact your local Analog Devices, Inc., account representative for specific product ordering information and to obtain the specific Automotive Reliability reports for these models. Rev. D Page of

24 ADA89-/ADA89-/ADA89-/ADA89- Data Sheet NOTES Analog Devices, Inc. All rights reserved. Trademarks and registered trademarks are the property of their respective owners. D85--/(D) Rev. D Page of