THE HYBRID active/passive electromagnetic interference
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1 IEEE TRANSACTIONS ON INDUSTRIAL ELECTRONICS, VOL. 54, NO. 4, AUGUST Analysis of Insertion Loss and Impedance Compatibility of Hybrid EMI Filter Based on Equivalent Circuit Model Wenjie Chen, Student Member, IEEE, Xu Yang, Member, IEEE, and Zhaoan Wang, Senior Member, IEEE Abstract The hybrid active electromagnetic interference filter HAEF) is considered one of the best options for improving power quality for a number of considerations. A systematic classification and identification of HAEF configurations is given, including their insertion losses, impedance compatibilities, potential applications, and comparative features. It is aimed at providing a broad perspective on the status of HAEF technology to researchers and application engineers dealing with EMI issues. The basis of discussion is an equivalent circuit model that includes all possible combinations of active and passive elements and matches these to the desirable attributes. The evaluation indicates those topologies that are known and those topologies that are relatively new. Index Terms Active filter, electromagnetic interference EMI), hybrid, model. I. INTRODUCTION THE HYBRID active/passive electromagnetic interference EMI) filter HAEF) is one of the key elements that are used in the battle against noise that is being conducted into or out of typical electronic devices. Many papers have discussed and proposed hybrid EMI filters or active EMI filters that are accompanied by a small passive component [1] [10], [12] [15]. Reference [1] gave a general concept of passive and active hybrid EMI filters. In [2], [3], [9], [10], and [12], a small passive filter is coupled with an active circuitry to attenuate the noise. The combination of these two schemes can lead to an improvement in the filter s attenuation performance over a wide frequency range. However, what they mainly focused on was active cancellation circuits, where a few of them seriously characterized and evaluated the hybrid system. Questions are, therefore, raised. How will these two kinds of filter passive and active) combine together when placed in one filter system? Is the attenuation the sum of the individual attenuation of each of the filters in the hybrid system? If there are several kinds of circuit configurations, a third question also comes to mind: How will each hybrid type perform when placed in the same environment? Answers to these questions may help circuit designers anticipate how their products will perform when evaluated for a specific application. Manuscript received November 24, 2005; revised November 17, This work was supported by the National Natural Science Foundation of China under Project The authors are with the State Key Laboratory of Electrical Insulation and Power Equipment, Xi an Jiaotong University, Xi an , China cwj@mail.xjtu.edu.cn). Digital Object Identifier /TIE Fig. 1. Concept of the conduction noise transmission system. In an effort to obtain answers to these questions, hybrid active EMI topologies are identified systematically by the following: describing appropriate models for passive EMI filters; determining the desirable attributes of an active circuit; generating possible topologies in a systematic fashion. This approach uncovers existing and new topologies, and establishes an equivalent circuit model for describing HAEFs. This paper is presented in five parts. Starting with an introduction, the HAEF equivalent circuit model, i.e., a two-port model with three elements, including all possible combinations of active and passive elements, is proposed in Section II. Based on the module, Section III covers the insertion losses ILs) of different configurations used, the impedance compatibilities, their potential applications, and the comparative features. Experimental results are presented in Section IV. Section V is the conclusion. II. EQUIVALENT CIRCUIT MODEL OF HAEF Fig. 1 shows the basic source/filter/load configurations of the system. Z s represents the impedance of the line impedance stabilization network LISN). represents an internal impedance of the noise source. HAEFs for solving EMI noise in power systems can provide the following functions: noise compensation; noise damping; noise isolation. In order to explain the operational principle more clearly, a simplified equivalent model of the passive and active filters is introduced first /$ IEEE
2 2058 IEEE TRANSACTIONS ON INDUSTRIAL ELECTRONICS, VOL. 54, NO. 4, AUGUST 2007 Fig. 3. Typical power line filter and its equivalent circuit. a) Typical power line filter. b) Equivalent circuit. Fig. 2. Generalized block diagram and configuration for active EMI filter. a) Parallel configuration. b) Series configuration. Active EMI filter topologies are generally classified in terms of noise that is sensed current or voltage) and the means of applying the cancellation signal by a current or voltage source). An alternative classification, according to circuit configuration and connections, is introduced in this paper, as shown in Fig. 2, which are of two basic types, namely: 1) parallel and 2) series. In parallel filters, the active component is an equivalent current source. According to the noise voltage or current that has been detected, the cancellation current is i c = A g u s or i c = A i i s. In series filters, the active component is an equivalent voltage source, and the cancellation voltage is u c = A u u s or u c = A r i s in terms of the noise that is sensed. Fig. 3a) shows a typical passive EMI filter configuration. A good filter has generally a common-mode CM) choke of at least a few millihenrys commonly in the range of 3 30 mh). CM capacitors are typically limited by safety considerations for ground leakage to values in the range of nf. The differential-mode DM) choke has a lower value typically < 1 mh) and sometimes does not exist as a discrete component but is made by the few percent leakage inductance of the CM choke. To simplify the discussion here, the initial focus is on canceling CM noise, but the basic technique can be applied equally to canceling DM noise. The equivalent circuit is shown in Fig. 3b). Generalized topologies may be identified by grouping combinations of passive elements with ideal active elements to construct filters of varying complexity. Fig. 4 shows the electrically valid connection for the basic topology. The three elements comprise a two-port network: one port acts as the input, while the other one acts as the output. When the filter is connected Fig. 4. Generalized topologies of HAEFs. to the ac source, as shown in Fig. 1, the input is quiet, and the output is noisy. On the other hand, when the filter is placed between a converter and its load, the input is noisy, and the output is quite. Note that this model can be utilized in various kinds of applications, such as input or output EMI filters and power filters. III. EVALUATION OF TOPOLOGIES Although all these basic HAEF circuits may achieve high attenuation for the EMI noise, they do have advantages and disadvantages respectively when considered from a practical point of view. All of the configurations that are presented may be evaluated in terms of the IL and impedance compatibility. It is aimed at identifying their inherent properties that make them particularly suitable or unsuitable for practical applications. A. IL The IL of a filter that is connected to a given transmission system is defined as the ratio of the voltage appearing across the line immediately beyond the point of insertion before U 1 )
3 CHEN et al.: ANALYSIS OF IL OF HYBRID EMI FILTER BASED ON EQUIVALENT CIRCUIT MODEL 2059 If there are only passive elements Z 1 and Z 2,theILis IL PEF = 1+ Z ) 1 + Z s. 3) Z 2 // That is, the effectiveness of the active component is mainly dependent on impedance Z 2 // and amplifier gain A r.the overall gain of the active filter should be larger than the impedance Z 2 // to obtain the maximum IL. If there is a capacitor load, the impedance decreases with the increase of frequency. Therefore, the type-i filter is more fit for the capacitor load. In Fig. 5b), the additional IL that is introduced by the active component is found as IL 2 = A i + A i Z 1 Z 2 // ). 4) Fig. 5. Comparison of the IL. a) Six types. b) Type-V filter with different gain. and after U 2 ) insertion. Using the A, B, C, and D parameters of the filter, it follows that IL = U 1 U 2 = A + B + CZ s + DZ s 1) where Z s and are the source impedance and load impedance, respectively. It is necessary to notice that the performance of a typical power line filter varies as the source impedance and load impedance vary. That is, filters are usually designed for 50-Ω input impedance and output impedance, but the conditions in real installation are different. In case of a type-i filter, as shown in Fig. 5a), the IL is readily found as IL 1 = 1+ Z 1 + Z s Z 2 // + A r Z 2 // ). 2) This condition implies that the active filter can provide IL irrespective of the passive impedance, particularly at a comparatively low frequency. If the internal impedance of the noise source is pretty larger than the receiver s impedance Z s ),theil can be approximated as gain A i. It means that a type-ii filter is suitable for the noise source that is close to an ideal current source. For good noise attenuation, gains A i should be as large as possible. In practice, to avoid instability, the loop gain must be restricted at high frequency, resulting in limited noise attenuation. As Z 1 /Z 2 // ) increases with frequency, the high-frequency noise is mainly attenuated by passive components. The IL of a type-iii configuration may be mainly determined by the active filter when A r Z 2. That is, the IL will obtain the maximum value no matter what kind of noise source it may be: capacitor, inductor, or fluctuated. It is suitable to all kinds of nonlinear loads. Another advantage of this configuration is that the active filter that is used in this type carried neither supply voltage nor fundamental current. In case of the type-iv filter, the additional IL that is introduced by the active component is found as IL 4 = A r. 5) It means that the IL that is provided by the active filter is always dependent on system impedance, Z s, and.if A r, the passive components may be redundant in this configuration. Under these conditions, the active element supports the entire noise and is equivalent to a single series active element alone. In case of voltage detection and when Z s,il may be as large as A u. It can be successfully applicable if the noise source is close to an ideal voltage source. The same argument can be applicable to the type-v filter. If the internal impedance of the noise source is pretty larger than the receiver s impedance Z s, its IL is proportional to amplifier gain A i. This condition implies that if the noise
4 2060 IEEE TRANSACTIONS ON INDUSTRIAL ELECTRONICS, VOL. 54, NO. 4, AUGUST 2007 TABLE I INSERTION LOSS OF BASIC HAEF TOPOLOGIES source, including its impedance, is close to an ideal current source that has infinite internal impedance, then a type-v filter is suitable for this application. In this manner, the configuration is equivalent to a single parallel filter. The final configuration is of type VI. The IL is dependent on both system impedance and passive impedance. Impedance Z 1 presents high noise and low fundamental impedance. This provides blocking for the noise currents, diverting these to the shunt path that is provided by Z 2. The fundamental current does not flow in the active element and is diverted to Z 1. Impedance Z 2 provides a path for the noise currents and high impedance at the fundamental. The aforementioned analysis is mainly focused on the filter with current-detection method. Table I presents a summary of this evaluation. Specifically, four observations are made. 1) The IL of the hybrid system is greater than the sum of the individual ILs of each of the filters. Although the efficiency of the passive element in the hybrid system is the same with that of a pure passive filter, the ILs of the active circuit in these six types are all increased compared with that of the pure parallel or series active cancellation circuit. It is because the introduction of passive elements changes the source/load impedance of the whole system. That is, there is a mutual or cooperative relationship between the passive and active elements in the hybrid system. 2) With respect to each hybrid type, the difference between the voltage- and current-detection methods only exists in the active part: The former is AZ s, and the latter one is A. This conclusion is consistent with that of the pure active filter. In other words, when Z s A r /A u and, for the type-i, type-iii, and type-iv filters, the voltage-detection method performs better than the current-detection method, and vice versa; for the type-ii, type-v, and type-vi filters, when Z s A i /A g, the current-detection method obtains greater IL than the voltage-detection method, and vice versa. 3) For the type-ii, type-v, and type-vi filters, the active part is the controlled current. The relationship between the active IL of the three types can be described as 1+ Z 1 Z 2 // = A i type-v ) A i type-ii + Z 1 A i Z s + Z 2 // 6) type-vi. It implies that, when considered under the same condition, the type-ii filter will achieve greater IL than that of the type-v and type-vi filters. 4) For the type-i, type-iii, and type-iv filters, a similar relationship also exists, which can be described as Ar ) Z 2 // type-i = Ar Z 2 type-iii + Ar 7) type-iv. Since the passive ILs of these types are identical, the type-i filter will achieve greater IL than the type-iii and type-iv filters. Fig. 5a) shows the IL of the six HAEFs under ideal conditions. In all cases, we assume that the active device has an open-loop gain of , the passive impedance is Z 1 = 15 mh,z 2 =10 nf), and the system impedance is = 100 pf,z s =50Ω). It has been demonstrated that no matter what kind of HAEF it is, the IL is improved compared with the pure passive EMI filter. Focused on the six hybrid types, it is found that ILII) ILV)+ILVI) 8) ILI) ILIII)+ILIV) 9)
5 CHEN et al.: ANALYSIS OF IL OF HYBRID EMI FILTER BASED ON EQUIVALENT CIRCUIT MODEL 2061 TABLE II INPUT/OUTPUT IMPEDANCE OF BASIC HAEF TOPOLOGIES which is exactly in accordance with the aforementioned theoretical analysis. These curves also indicate that, under the assumed conditions, the type-ii hybrid filter can achieve the greatest IL. Fig. 5b) compares the effect of active close-loop gain on the IL, which is analyzed for the type-v filter, and the gain of the active component is 0, 10, 20, and 50, respectively; a similar conclusion may be drawn in other types of filters. It could be seen that, at 10 khz, the hybrid circuit when A =10) improves attenuation by 20 db over the passive-only case when A =0). In addition, with the increase of gain, IL also increases. From the results, it was concluded that the hybrid filter with greater gain will provide more attenuation than that with lower gain. This also emphasizes the fact that loop gain has a significant effect on the performance of the hybrid EMI filter. B. Impedance Compatibility For a selected topology, the attenuation is also determined by the impedance of the filter components and the characteristics of the LISN and drive noise source. Once we can model the impedance-frequency characteristics, the attenuation of the filter along the frequency range of concern can be calculated. The input/output impedance expressions for the basic topologies by different noise detection methods are given in Table II. These impedances, i.e., Z i and Z o, will be used to choose for an appropriate hybrid filter. As illustrated in Fig. 1, when the impedances at port B between the load and the filter are not matching, the highfrequency noise will be reflected at this interface. If Z i the input impedance of the filter) and Z o the output impedance of the filter) are all unequal to its respective outer impedance, i.e., Z s and, the EMI noise will be reflected in both interfaces. Thus, in order to acquire better noise attenuation performance, an EMI filter should be designed in a way to obtain maximum impedance unmatching not only with the load but also with the source. Detailed discussions about the impedance compatibility requirements can be found in [8]. From the results that are shown in Table II, it can be analyzed that, for the topologies of the type-i, type-iii, and type-iv filters, when A u Z s = A r, the impedance Z o are identical. The type-ii, type-v, and type-vi filters have identical output impedance if A g Z s = A i. Thus, the following discussions are mainly based on filter with current detecting method. Compared with pure passive filter output impedance Z 2 //Z 1 + Z s ), the impedance Z o of type-i, type-iii, type-iv, and type-vi filters are all increased to a certain extent. According to impedance unmatching criteria, these topologies are suitable to those sources with small internal impedance. Since there is a distinct improvement in the impedance of the type-iv filter, it is much more fit for the noise source that is close to an ideal voltage source. As Z o of the type-ii and type-v filters decreased, those filters are suitable to the high impedance source. Since the input impedance of the passive filter is Z 1 + Z 2 //, Z i increased in all kinds of hybrid filters with current detection. While for the voltage-detection one, Z i diminished. The former is fit for the low-impedance load, and the latter one is fit for the high-impedance one. The relationship between input/output impedance and frequency is shown in Figs. 6 and 7, respectively. It is necessary to notice that the noise impedance is assumed as = 100 pf, and this is the reason for the similar input impedance curve between the passive component and the type-iii filter. It is also evident from Fig. 7 that type-i and type-iv filters have similar output impedance curve. IV. PRACTICAL FILTER IMPLEMENTATION In this section, several experiments are made to evaluate the performance of the basic topologies. The active EMI filter that
6 2062 IEEE TRANSACTIONS ON INDUSTRIAL ELECTRONICS, VOL. 54, NO. 4, AUGUST 2007 Fig. 6. Comparison of input impedance. Fig. 7. Comparison of output impedance. is proposed in [10] and [11] is used as an extended example of the hybrid active EMI filter. The prototype is shown in Fig. 8. A 600-W power supply for a personal computer operating at 33 khz is used as a high-frequency noise source. A LISN is used to provide the stable source impedance at high frequency, and an E7401A electromagnetic analyzer as well as a CM noise separator is used in the measurement of the conducted CM spectrum. For EMI standard EN55022, the sweep range is in the range of 150 khz 30 MHz. Figs. 9 and 10 show the measured CM spectrum of the equipment under test EUT) with and without LC low-pass EMI filter. For the test, the CM choke that was used was 13 mh, and the Y capacitor that was used was 1 nf. It can be seen that, without any EMI filter, this power supply cannot pass the EN55022 limit over the entire frequency range. Furthermore, it is observed that the low-frequency noise is a major issue to pass the EMI requirement. Without increasing the value of the CM choke or using multistage EMI filters, the noise in the range of MHz cannot be reduced further. Fig. 8. EMI noise measurement setup. a) Active EMI filter. b) EUT. c) Configuration of experiment system. Fig. 11 shows the conducted EMI spectrum when the proposed hybrid active EMI filter is added into the system. Two topologies were tested. In the first topology type-v filter), the active circuit faces the input of the noise source. In the second topology type-ii filter), the Y capacitor faces the input of the noise source. The main consideration we choose these types is that the character of the CM noise source under test is close to a current source. From the result, it was concluded that the topology of the type-ii filter provided more attenuation than that of the type-v filter, which is in accordance with the aforementioned simulations and analysis. This result also emphasizes the fact that impedance compatibility has a significant effect on the performance of the EMI filter. By introducing the combination of active and passive filters, one can dramatically increase the amount of noise attenuation that is attainable for the hybrid system. These two complementary filtering schemes allow for the maximum usage of the injector.
7 CHEN et al.: ANALYSIS OF IL OF HYBRID EMI FILTER BASED ON EQUIVALENT CIRCUIT MODEL 2063 Fig. 9. No EMI filter installed. Fig. 10. Passive EMI filter installed. V. C ONCLUSION Hybrid active EMI filters have been evolved and used in practices as a cost-effective solution for the attenuation of EMI noise. Existing publications focus mainly on the active cancellation circuit. There is a lack of published material that provides a comprehensive analysis of the hybrid active/passive filter. This paper has been aimed at filling this gap. In this paper, we have proposed an equivalent circuit model for HAEF, which includes six possible combinations of passive and active elements. Then, the IL and impedance compatibility of each topology were described in detail. To facilitate the understanding and selection of particular configurations for a given application, the evaluation is based on two main criteria: 1) the circuit configurations of hybrid filters and 2) the noise impedance of the compensated system. This paper has also taken into account the interaction between the passive component and active circuit in HAEF. It Fig. 11. Test results of proposed hybrid topologies. a) HAEF of type-v. b) HAEF of type-ii. is found that the multistage passive filter can be replaced with a small-sized one that deals mainly with high-frequency noise in the hybrid system. While at comparatively lower frequency, the active filter is dominant. The active component s demerit of narrow bandwidth can also be overcome with ease. The HAEF can be considered as a better alternative for EMI noise attenuation, owing to reduced cost, simple design and control, and high reliability compared to pure passive or active filters. This paper has also uncovered several new topologies, which can be further explored. It is obvious from the contribution that a great deal of work still needs to be done. REFERENCES [1] A. C. Chow and D. J. Perreault, Design and evaluation of a hybrid passive/active ripple filter with voltage injection, IEEE Trans. Aerosp. Electron. Syst., vol. 39, no. 2, pp , Apr [2] M. Zhu, D. J. Perreault et al., Design and evaluation of feed-forward active ripple filters, IEEE Trans. Power Electron., vol.20,no.2,pp , Mar
8 2064 IEEE TRANSACTIONS ON INDUSTRIAL ELECTRONICS, VOL. 54, NO. 4, AUGUST 2007 [3] Y.-C. Son and S.-K. Sul, Generalization of active filters for EMI reduction and harmonics compensation, in Proc. 38thIEEE IAS Annu. Meeting, Oct , 2003, pp [4] P. Cantillon-Murphy, An active ripple filtering technique for improving common-mode inductor performance, IEEE Power Electron Lett.,vol.2, no. 2, pp , Jun [5] T. Nussbaumer et al., Differential mode input filter design for a threephase buck-type PWM rectifier based on modeling of the EMC test receiver, IEEE Trans. Ind. Electron., vol. 53, no. 5, pp , Oct [6] B.-R. Lin and C.-H. Huang, Implementation of a three phase capacitor clamped active power filter under unbalanced condition, IEEE Trans. Ind. Electron., vol. 53, no. 5, pp , Oct [7] M. E. Ortúzar et al., Voltage-source active power filter based on multilevel converter and ultracapacitor DC link, IEEE Trans. Ind. Electron., vol. 53, no. 2, pp , Apr [8] D. C. Hamill, An efficient active ripple filter for use in DC-DC conversion, IEEE Trans. Aerosp. Electron. Syst., vol. 32, no. 3, pp , Jul [9] A. C. Chow and D. J. Perreault, Design and evaluation of an active ripple filter using voltage injection, in Proc. IEEE Power Electron. Spec. Conf., Jun , 2001, pp [10] Y. C. Son and S.-K. Sul, A new active common-mode EMI filter for PWM inverter, IEEE Trans. Power Electron., vol. 18, no. 6, pp , Nov [11] B. H. Cho et al., Analysis and design of multi-stage distributed power system, in Proc. INTELEC, 1991, pp [12] W. Chen, X. Yang, and Z. Wang, An active EMI filtering technique for improving passive filter low frequency performance, IEEE Trans. Electromagn. Compat., vol. 48, no. 1, pp , Feb [13] K. Al-Haddad and A. Chandra, A review of active filters for power quality improvement, IEEE Trans. Ind. Electron., vol.46,no.5,pp , Oct [14] N. Mutoh et al., New methods to suppress EMI noises in motor drive systems, IEEE Trans. Ind. Electron., vol. 49, no. 2, pp , Apr [15] D. Rivas et al., Improving passive filter compensation performance with active techniques, IEEE Trans. Ind. Electron., vol.50,no.1,pp , Feb Wenjie Chen S 06) was born in Xi an, China, in She received the B.S. and M.S. degrees in electrical engineering from Xi an Jiaotong University, Xi an, in 1996 and 2002, respectively. She is currently working toward the Ph.D. degree at the same university, with her research focused on the EMI and integration design of power electronics modules. Since 2002, she has been a member of the faculty of the School of Electrical Engineering, Xi an Jiaotong University, where she is currently a Lecturer. Her research interests include soft-switching dc/dc converters and active filters, and power electronic integration. Xu Yang M 02) was born in China in He received the B.S. and Ph.D. degrees in electrical engineering from Xi an Jiaotong University, Xi an, China, in 1994 and 1999, respectively. Since 1999, he has been a member of the faculty of the School of Electrical Engineering, Xi an Jiaotong University, where he is currently a Professor. From November 2004 to November 2005, he was with the Center of Power Electronics Systems, Virginia Polytechnic Institute and State University, Blacksburg, as a Visiting Scholar. He then returned to the School of Electrical Engineering, Xi an Jiaotong University, where he has been engaged in teaching and research in the power electronics and industrial automation areas. His research interests include soft-switching topologies, PWM control techniques and power electronic integration, and packaging technologies. Zhaoan Wang SM 98) was born in Xi an, China, on June 9, He received the B.S. and M.S. degrees from Xi an Jiaotong University, Xi an, in 1970 and 1982, respectively, and the Ph.D. degree from Osaka University, Osaka, Japan, in From 1970 to 1979, he was an Engineer at the Xi an Rectifier Factory. Since 1982, he has been with the School of Electrical Engineering, Xi an Jiaotong University, where he was a Lecturer and is currently a Professor. He has published more than 150 technical papers and has led numerous government and industry-sponsored projects in the areas of power and industrial electronics. He is engaged in research on power conversion systems, harmonics suppression, reactive power compensation and power electronic integration, and active power filters.
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