Voltage Controlled SAW Oscillator Mechanical Shock Compensator

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1 Voltage Controlled SAW Oscillator Mechanical Shock Compensator ECE Senior Design II Spring 2013 Final Design Report UConn ECE Project Members: Joseph Hiltz-Maher Max Madore Shalin Shah Shaun Hew UConn Faculty Advisor: Helena Silva, Ph.D. (ECE) Phonon Advisor: Scott Kraft

2 2 Table of Contents [1] Abstract..[3] [2] Background...[3] [3] Theory [4] [3.1] VCSOs... [4] [3.2] Acceleration Sensitivity. [6] [4] Methods [7] [4.1] Compensation....[7] [4.2] Testing... [8] [4.3] Issues and Fixes...[11] [4.3.1].....[11] [4.3.2].....[11] [4.3.3].....[11] [4.3.4].....[12] [4.3.5].....[12] [5] Experimental Results...[13] [5.1] x-axis [13] [5.2] y-axis [15] [6] Discussion of Results... [16] [7] Timeline...[17] [8] Cost Analysis....[18] [9] Conclusions and Recommendations....[18] [10] Appendix....[19] [10.1] Function Generator Calibration Code....[19] [10.2] Shock Response Trial Code...[19] [11] Project Collaborators.....[21] [12] Works Cited [21]

3 3 [1] Abstract: Under mechanical shock, the output frequency of Voltage Controlled Surface Acoustic Wave (SAW) Oscillators (VCSO) experiences a significant shift due mostly in part to the physical disturbance of the SAW crystal resonator. The resulting phase noise, or time domain jitter, causes concerning levels of frequency inaccuracies for the VCSO s high precision applications. As a world leader in the SAW industry, Phonon Corporation is looking to offer improved VCSO acceleration sensitivity to their aerospace and defense clients. To achieve this goal of multi-axis mechanical shock compensation, the shock experienced by the system is measured by an accelerometer and output as a corresponding voltage. This voltage is filtered via a compensation circuit and fed into the frequency control pin of the VCSO. As a result, any frequency shift due to shock is canceled by an equal and opposite shift from the VCSO s control circuit, yielding a consistent frequency output. In this study, a previously designed test method was improved and utilized to show the success of the above compensation method and that 0 th order compensation is sufficient to improve the acceleration sensitivity of the oscillator in question by more than 15dB. [2] Background: Phonon Corporation, founded in 1982 in Simsbury, Connecticut, is a global leader in the design and manufacture of SAW (Surface Acoustic Wave) components and devices. Their primary clients reside in the aerospace and defense industries, where a high level of precision is a necessity. One device incorporating SAW technology that Phonon currently manufactures is the Voltage Controlled SAW Oscillator (VCSO). VCSOs employ a SAW crystal resonator as a high- Q bandpass filter to control, and allow fine tuning of, the output of a transistor oscillator circuit [1][2]. An inherent issue with all SAW devices is their mechanical shock sensitivity due to the effects of acceleration on the SAW crystal itself, resulting in frequency inaccuracies. In order to improve the acceleration sensitivity of their oscillators and thereby improve frequency stability, Phonon is looking for an analog solution to provide at least 20dB of vibration compensation along any axis. They are especially concerned with vibration frequencies below 2 khz, as higher frequency vibrations can be readily dealt with using mechanical, rather than electrical, solutions. The resulting compensation circuit must also be small enough to fit within the preexisting oscillator 1 x1 x0.255 flat-pack casing and inexpensive enough to not drastically effect component pricing. VCSO devices can be found in any system utilizing oscillators with specific applications in radar, communications, navigation, and electronic warfare. In a radar system, a VCSO can generate the electromagnetic waves used to determine the location of an object by recording the time it takes for the wave to travel to and from the target [3]. If, however, the VCSO is onboard an airplane experiencing turbulence, the ability of the VCSO to accurately keep time is severely hindered by the acceleration. This in turn would cause the radar system to incorrectly calculate the locations of targets, rendering it useless. Thus for these systems to operate correctly, they

4 4 require that the output of a VCSO contain as little phase noise as possible and therefore maintain as stable a frequency as possible [4]. The initial stages of this project started in the Fall Semester of 2011 with a previous UConn senior design team, where the use of an accelerometer compensation system was studied. The most important thing carried over to this study was the creation of a mechanical shock tower and the given testing and solution methods. Work was also done during the summer of 2012 by Phonon Corporation, yielding promising results from tests with shocks in one axis. This is the point at which this year s project began. [3] Theory: [3.1] VCSOs The Voltage-Controlled SAW Oscillator we are using is the oscillator listed on Phonon s product library [1]. The oscillator is essentially an amplifier circuit which outputs a signal at a desired frequency. The voltage controlled oscillator takes advantage of feedback and allows a reading of the output voltage to both stabilize and change the output frequency if necessary. This section will provide a basic understanding of oscillator circuits and how the voltage controlled frequency adjustment was used on the oscillator of this project. By using feedback circuits, the variance from ideal output frequency can be measured and fed back into the amplifier, in a self-correcting manner. Due to the Barkhausen criterion for stability, it has been established that to create an oscillating output the closed loop gain of the amplifier circuit must be greater than unity. If it is exactly unity, a perfectly sinusoidal wave will result, but a gain greater than unity will still provide an oscillating output signal. It is also necessary for the phase shift to be 0 or some multiple of 2π [5]. V in V out Figure 1: A simple feedback system with amplifier A and feedback network β π π In this particular oscillator, with no control voltage applied, the frequency is set to MHz, meaning the expected output should be centered around a MHz signal when it is turned on. This models a simple XO, also known as a crystal oscillator, when the frequency control input is not being utilized [3]. The VCSO is designed to operate at 400 MHz when a control voltage of 1V is applied [6]. The oscillators provided for this shock sensitivity study, however operate outside of tolerance and thus show a higher than normal operating frequency. The point of having a VCSO is that it is sometimes necessary to alter the output frequency by pulling or pushing the frequency with a bias voltage. In these types of circuits a crystal oscillator is used. Crystal oscillator circuits can be represented as an equivalent schematic

5 5 of discrete RLC circuit components [7]. Oscillation can be achieved by using either op-amp or transistor amplifier circuits. By adding capacitances and inductances in, the circuit can be tuned at the input or the output. The advantage of the crystal over the lumped component counterpart is the high-q properties which allow for reduced phase noise at high frequencies. Phase noise is the frequency domain representation of jitter, which is undesirable in timing sensitive circuits such as oscillators. A quartz crystal is a typical material for these operations, because of their unique piezoelectric properties. The crystal has a natural resonant frequency which sets the frequency at which the oscillator will naturally operate. In the RLC equivalent circuit, this is similar to choosing values of L and C where the resonant frequency occurs at [7]. In order to sway the output voltage away from its natural frequency, the crystal is put in series with a capacitor. This capacitor alters the reactance of the RLC equivalent circuit causing the resonant frequency to change. In the case of the Voltage Controlled Oscillator, a variable capacitor diode, also known as a varactor, is placed in series and is controlled by an applied voltage, ranging from 0-5 volts, in this case [6]. A varactor is a specialized reversed biased diode, where the applied voltage will increase or decrease the depletion region between the P and N type materials [8]. In Equation 3, it is shown that capacitance is a result of the permittivity of the material times the surface area of the charges, divided by the distance between the charged regions. Thus, a low bias voltage results in a narrow depletion region and a higher capacitance, since the distance between the charged surfaces is small, while a high bias voltage increases the depletion region, decreasing the capacitance. By using this variable capacitance in series with the crystal, an oscillating output of our choice can be established [9]. Figure 2 shows the effects of varactor frequency control on one of the VCSOs used in this study. The plot of measured output frequency versus control voltage shows that as voltage is increased, the frequency output of the VCSO shifts accordingly in a characteristically nonlinear fashion. Figure 2: Measured Frequency Response to an Applied Control Voltage

6 6 [3.2] Acceleration Sensitivity The oscillator system described above has proven very effective in environments free of acceleration. The project goal was to design a circuit which can continue this form of controlled signal generation, even under systems with external shock. The main cause of distortion is the crystal itself, which operates on piezoelectric principles. Any external force applied will distort the output, creating frequency shifts away from the desired frequency. Under acceleration, the SAW crystal flexes against its mounting structure in response to the applied force [10]. This flexing alters the propogation length of the signal across the crystal between the reflectors and interdigital transducers, distorting the ouput frequency [11]. If the oscillator is struck in the positive x direction, as defined in Figure 3, the propagation lengths will increase slightly, causing an increase in the resonant frequency of the oscillator, and therefore an increase in the total output frequency. A strike in the negative x direction will cause the crystal to flex in the opposite direction, decreasing the propagation length and output frequency. Due to the relative regidity of the crystal along the y and z axes, it is expected that acceleration in these directions will have much less of an effect on the oscillator s frequency as compared to the x axis [10]. Figure 3: A SAW Resonator Diagram with Reference Axes [11]

7 7 [4] Methods: [4.1] Compensation: To achieve mechanical shock compensation, the topology of Figure 4 was developed and shown effective by the previous senior design team and Phonon. In this design, an accelerometer is used to measure the shock experienced by the system, outputting a voltage linearly related to the amount of acceleration. This voltage is used to adjust the frequency of the VCSO. The accelerometer must be compact, able to measure appropriate magnitudes of shock, inexpensive, and have a bandwidth of at least 2 khz. The ADXL001 series, single axis accelerometers produced by Analog Devices used in this study met all of these criteria. Its high bandwidth of 20 khz was especially desirable as most compact MEMS accelerometers struggle to reach even the 2 khz range. Figure 4: Solution Topology Block Diagram Before the output of the accelerometer reaches the VCSO, it is passed through an analog filter. A 0 th order resistive voltage divider has been shown to provide significant shock compensation since most, if not all, frequency deviation due to acceleration is directly proportional to the magnitude of acceleration experienced by the SAW crystal. As a result, the accelerometer voltage must merely be scaled down to cause the appropriate compensating frequency shift. The frequency adjustments caused by the control pin on the VCSO, however, are not linear, as shown in Figure 2 above. The most linear point on the control curve is located at 1V, and since the typical amount of frequency correction necessary is around 100 Hz, the area of operation can be assumed linear. Figure 5 shows the 3-axis, 0 th order compensation network with the 1V operation point used in this study. A non-inverting summing amplifier is used to superimpose the accelerometer outputs of each compensation axis as well as set the operation point. Using the acceleration sensitivities of the oscillator and accelerometer and the frequency sensitivity of the control input, the total necessary attenuation of the circuit can be determined as will be shown.

8 4 ST Vdd2 8 4 ST Vdd2 8 4 ST Vdd V COM 7 Vdd 6 Xout 5 +5V ADXL COM 7 Vdd 6 Xout V 4 V- 1 OUT TLC2262/101/TI 8 V+ +5V Vcontrol GND 16 Vcc RFout +12V +5V 0 ADXL COM 7 Vdd 6 Xout 5 ADXL V Figure 5: Compensation Circuit Diagram [4.2] Testing: To determine the acceleration sensitivity of the VCSO and test the compensation method, the testing configuration of Figure 6 was developed based upon previous work and physically realized as shown in Figure 7. Figure 6: Testing Configuration Block Diagram Figure 7: Physical Testing Setup Each shock trial began with the MATLAB script shown in Appendix This script performs a short period of data collection using a National Instruments X series USB-6353 Data Acquisition Card (DAQ) to collect and plot data from a Hittite HMC439QS16G Phase Frequency Detector (PFD). The PFD compares the signal from a Giga-tronics 6060B Signal Generator to that of the 400MHz VCSO and outputs a voltage proportional to the phase difference between the two. Figure 8A depicts the parameter measured by the PFD. This makes comparing high frequency signals easier, as when the signal frequencies are matched, the PFD outputs a constant voltage, indicating a constant phase difference (Figure 8B). When the frequencies are mismatched, the PFD outputs a triangular wave showing the constantly increasing and wrapping phase difference between the signals (Figure 8C). The function of this first MATLAB script is thus to observe the output of the PFD and adjust the signal generator s frequency accordingly to match the VCSO. Typically, many iterations of this code are needed to

9 9 finally achieve calibration. When a shock pulse occurs, the short period of phase deviation caused by a temporary frequency shift of the VCSO is evident by a perturbation in the output voltage of the PFD. Due to the extreme sensitivity of the VCSO to its environment and the inability to control the signal generator frequency in increments finer than 10 Hz, it was typically difficult to obtain perfect alignment between the signal generator and VCSO. Recalibration generally took place just before each shock trail. An output characterized by Figure 8B showing a negative voltage with a thicker plot tended to give the best results with the least noise produced by the PFD. Figure 8: A. Phase Difference [12] B. PFD Output: Matched Signals C. PFD Output: Unmatched Signals The output of the Hittite HMC439QS16G PFD is separated into two parts, the difference of which produces the phase plot. This subtraction can be done by setting up the DAQ in differential mode, however because the other sources of data did not require differential mode, the DAQ inputs were made simpler by performing the subtraction with a differential op amp circuit. The circuit in Figure 9 shows some other advantages of this method in addition of gain to increase resolution and the use of a hardware low pass filter to remove high frequency noise. The output of the op-amp also provides a convenient test point for an oscilloscope, which could be used to calibrate the system in place of the MATLAB script described above. Figure 9: Differential Op-Amp Circuit with Low Pass Output Filter Figure 10: Transistor Switching Circuit Immediately after matching the signal generator s frequency to the VCSO s frequency, a second MATLAB script, shown in Appendix 10.2, is used to run an actual shock trial. This script initializes and reads analog inputs on the DAQ, collecting, filtering, processing, plotting and storing data from the PFD and accelerometer mounted to the VCSO. This code also generates a

10 10 5V pulse of a specified duration from the DAQ to switch on the shock tower solenoid using the Darlington pair BJT transistor switching circuit of Figure 10. When the transistors are turned on, the circuit through the solenoid is completed, generating a large magnetic field that rapidly drives a metal rod within the solenoid up to strike the oscillator with considerable force. Accelerations in the hundreds of g s are desirable to generate an easily measurable frequency deviation in the VCSO. To make testing in multiple axes simpler, two shock towers were set up utilizing different aluminum packages to hold the oscillators and accelerometers in the proper orientation (Figure 11). The phase shift between the VCSO and signal generator resulting from a shock is sensed by the PFD and sent to the computer through the DAQ. There, the output voltage representing the phase is used to generate instantaneous frequency data by converting the voltage to radians and taking the derivative of the phase. Figure 11: Shock Tower Setups for x and y Axis Testing The outputs of the accelerometers are also collected by the DAQ and feed into the compensation the circuit as seen in Figure 12. This circuit is similar to the one of Figure 5 with the addition of potentiometers to quickly adjust the operating point and attenuation level of the accelerometer output and switches to toggle compensation for each axis and the operating point voltage shift. The physical realization of this circuit is shown in Figure 13. Figure 12: Compensation Test Circuit

11 11 Figure 11: Physical Realization of the Compensation Test Circuit After running a successful uncompensated trial, the attenuation ratio,, of the accelerometer output necessary to achieve compensation can be calculated using Equation 4. Here, is the peak change in accelerometer output voltage from its zero g value, is the peak instantaneous frequency deviation, and is the slope of the frequency control curve of the VCSO at the current operation point. ( ) Using this attenuation ratio, the potentiometer on the compensation test circuit for the axis being studied can be adjusted to set the proper voltage ratio between the input and output of the voltage divider. With compensation switched on, the process can be repeated to observe the success of compensation and make adjustments to the attenuation ratio as necessary. [4.3] Issues and Fixes: [4.3.1] Phase Frequency Detector Failure A major problem the 2012 senior design team encountered was constant failure of the PFD. During this study, it was discovered that the absolute maximum allowable input to the PFD is 13dBm and the VCSO outputs in the range of 10 to 12 dbm [13][6]. By placing a pad in line with the VCSO, the PFD failure rate was reduced significantly. The PFDs still displayed a high sensitivity to static shock and a general degradation of the quality of their output over time, however. [4.3.2] Broken Accelerometer After receiving the first ADXL Z accelerometer for this study, it was observed that the output saturated at accelerations considerably less than expected. The accelerometer was confirmed faulty using a calibrated accelerometer from Phonon, causing significant delays to the project while waiting for new ADXL Zs to be delivered. [4.3.3] Erroneous Vibration To promote repeatable, reliable results, steps were taken to ensure that the only acceleration felt by the system was the direct result of a single shock tower strike. The shock towers were delivered wrapped in foam to eliminate resonance in their metal structures and wires leading to components on the towers were taped together to prevent extra oscillations. The largest improvement to the shock tower setup was the addition of nylon straps to firmly hold the VCSOs in place. Without straps, the oscillators tended to jump off the shock tower and other

12 12 methods employed to secure them were either unreliable, too variable, or generated more resonance. The nylon material proved excellent at absorbing resonance of the aluminum accelerometer fixtures as well. The resulting setup from these tasks can be seen in Figure 14. Two final steps taken to improve shock response data were the removal of the oscillator package cover to prevent an oil canning phenomena that would not only introduce resonance but alter parasitic capacitances to the SAW crystal, and the inclusion of spring shim within the oscillator package to prevent internal parts from shifting during acceleration. Figure 14: Vibration Reduction Methods [4.3.4] Noise To decrease noise in the testing system, a hardware low pass filter was implemented at the output of the phase frequency detector differential op amp as discussed above. Software Butterworth low pass filters were also implemented, as shown in Appendix 10.2, to filter noise out of the instantaneous frequency and accelerometer data sets. Due to the fact that this study was only concerned with vibration frequencies under 2 khz, the filter cutoffs could be set relatively low. A major source of noise around 1 khz, however, was the PFD. If the inputs to the PFD were not perfectly matched, the noise level in the instantaneous frequency plots increased to ±5Hz. Under the frequency matching condition shown in Figure 8B, this noise level decreased to ±1Hz, making compensation confirmation much more feasible. This condition, however, can be difficult to obtain. Decreasing the noise of the system to the noise floor of the VCSO itself is key to studying the maximum compensation possible. [4.3.5] Ghosting Another major issue was discovered when features of the accelerometer output plot were observed to copy over to the PFD output plot and vice versa. Through consulting the National Instruments support literature, the phenomenon was labeled as ghosting. Ghosting is an issue inherent with all scanning data acquisition cards, as they only contain one analog to digital converter (ADC). To collect data from multiple sources simultaneously, the ADC switches between the inputs using a multiplexor. If the signal source has a high output impedance, it creates an effective low pass filter with the internal capacitance of the ADC. This causes the settling time of the ADC to increase significantly as it switches between input channels, meaning the proper voltage may not be recorded if the switching speed is too high [14].

13 13 Figure 15: Diagram of the Operation of a Data Acquisition Card [14] In order to resolve this issue, the sampling rate of shock trials was decreased significantly, but even with only two inputs, ghosting was still noticeable, especially when zeroing in on maximum compensation. When the accelerometer data ghosts over to the PFD data, the instantaneous frequency is also affected, as it is the derivative of the PFD data, causing the derivative of the accelerometer output pulse to show up in the frequency deviation curve. The only way to eliminate ghosting completely is to either use a different DAQ with multiple ADCs or sample from only one channel per trial. The repeatability of data seen during this study makes the one channel per trial method feasible, but not ideal. [5] Experimental Results [5.1] x-axis Figure 16: Uncompensated x-axis Results

14 14 Figure 17: Compensated x-axis Results Figure 18: Welch Power Spectral Density Estimate of the x-axis Frequency Deviation

15 15 [5.2] y-axis Figure 19: Uncompensated y-axis Trial with Ghosting Figure 20: Uncompensated y-axis Trial without Ghosting

16 16 Figure 21: Welch Power Spectral Density Estimate of the y-axis Frequency Deviation [6] Discussion of Results As seen in Section 5.1 above, x-axis testing yielded significant levels of compensation. Figure 16 depicts uncompensated results as a composite of two separate shock trials with and without the accelerometer input to the DAQ to prevent ghosting on the phase frequency data. This is the reason for the timing mismatch between the accelerometer pulse and the frequency deviation pulse as the solenoid does not run at exactly the same time every trial. The length of the solenoid power on time, however, is always exactly equal to the pulse length set in the shock trial code of Appendix This is confirmed by the two frequency deviation events that appear before and after the acceleration event representing the EM disturbance of the VCSO by the solenoid at its turn on and turn off times respectively. The accelerometer pulse of Figure 16 equates to a peak acceleration of 643g, causing an uncompensated frequency deviation of Hz. In Figure 17, compensation reduced the effects of a 691g peak acceleration to a maximum frequency deviation of -7.6Hz. The Welch power spectral density estimate of the shock pulse duration shows a total attenuation of 10 to 20 db depending on the frequency. These levels of compensation are both consistent and repeatable. The y-axis results of Figures 19 and 20 plainly show the adverse effects of even minimal ghosting. In Figure 19, a relatively large frequency deviation is seen to accompany the accelerometer pulse, following an 18ms on time for the solenoid. Two interesting observations about this deviation, however, are that its shape is the derivative of the accelerometer output and that it is not possible to compensate for it. By simply grounding the accelerometer input to the DAQ, shown in Figure 20, the solenoid turn on and turn off frequency deviations still occur, however the large event where the shock pulse takes place (using Figure 19 as a reference) has been removed. A very small event can be seen at this point, however it is barely above the noise level. The Welch power spectral density estimate of Figure 21 confirms that there is indeed an increase in frequency deviation at this point as compared to four regions of no acceleration.

17 17 [7] Timeline Figure 22: Timeline of the Project Progress In the first semester the team began meeting with faculty advisor Professor Silva in week 2, and an initial meeting with a Phonon Corporation representative Scott Kraft in week 3 was arranged. The group began to see how the given components functioned in week 3, and initial testing continued throughout the semester. The group members were rather inexperienced with Voltage Controlled SAW Oscillators, so the group collectively engaged in research regarding the VCSO. This was aided by Andrew, another Phonon employee, who supplied some documentation and background research. With the importance of accelerometers to the project, serving as the sensors for mechanical shock, research began to decide if other accelerometer technologies would provide better results. In the end the ADXL Z was decided upon and brought to the lab in week 11, concluding the majority of research and beginning compensation testing. In week 11 a Phonon visit occurred before Thanksgiving break which included a proposal for compensation. The semester ended with the team beginning to test compensation in the x-axis, which was not fully achieved. In the second semester the group continued doing research into single axis response. The first issue was unreliable data, which meant that testing methods were in question. Many shock trials were run trying to find average peak values from the Phase Frequency Detector and accelerometer outputs. During this process it was discovered that the accelerometer was oversensitive to shock, constantly displaying a saturated voltage of 5V during accelerations that were well within its supposed measurable range. While waiting for the accelerometer, the team was able to implement various filters (both hardware and software) to the current circuit to visualize cleaner results. A minor disturbance occurred in week 16 when a blizzard occurred on the exact day of planned trials and a meeting, but a substitute meeting was held the following Tuesday. In other weeks an instantaneous frequency plot was developed to measure the frequency deviation, and using this calculation the team was able to plan what would occur when a proper accelerometer was attached. Once a functional accelerometer was finally obtained and implemented (week 24), reliable, consistent results from the x-axis were recorded. X-axis

18 18 compensation was then quickly achieved. Research and testing also began on the y-axis under shock using a second shock tower that week. The final compensation circuit was completed before the presentation in week 26, and the team completed the final research paper and poster on time prior to the May 3 rd deadline. [8] Cost Analysis: Many of the items required for testing were already owned by Phonon or the University of Connecticut and were hence provided free of charge. These items included a National Instruments X series USB-6353 Data Acquisition Card, NI-DAQmx software for the DAQ, MATLAB 2009, a Giga-tronics 6060B signal generator, two Phonon 400MHz VCSOs, a B&K 9130 triple-output power supply, a second triple output bench power supply, an oscilloscope, phase-frequency detector development boards, two 24V solenoid shock towers, wire, and other passive circuit components. A budget from Phonon was not officially proposed, however the actual money spent this year on materials was much lower than typical senior design budgets of $1000. Listed in the Table 1 are the total estimated expenses for this project, broken down into the necessary hardware for building the compensation circuit and the components the group used to run tests during the project. Resistors (x12) 0.11 Op-Amp (x1) 2.08 Accelerometer (x2) Compensation Components BJT (x2) 2.16 Switches (x3) Op-Amp (x1) 2.08 Capacitor 0.04 Resistors (x5) 0.05 Straps (x2) Electrical Tape 5.79 Rubber Glove 3.80 Phase-Freq Detectors (x2) Testing Components TOTAL $ Table 1: Cost analysis including compensating circuit required parts and project testing components [9] Conclusions and Recommendations It is the conclusion of this study that compensation of up to 20dB is achievable along the x-axis of the oscillator. Due to the low acceleration sensitivity of the y and z axes, the testing method used here is not sufficient. The noise level introduced to the system by testing elements, especially the phase frequency detector, is unacceptable for achieving maximum compensation. Future testing should also check whether acceleration is taking place in an unintended direction, which would cause a false frequency deviation when studying the less acceleration sensitive

19 19 axes. Also, a data acquisition card with multiple ADCs would improve results by eliminating the possibility of ghosting. Once the noise floor of the testing system has been decreased, other possible causes of acceleration sensitivity can be explored including the possibility of frequency dependence that would warrant the use of higher order compensation filters. [10] Appendix [10.1] Function Generator Calibration Code %Senior Design Team 165 %Initial DAQ test with function generator as Analog Input figure(3) %define input device as the NI-DAQ, its device ID is Dev1 %device ID determined through daqhwinfo('nidaq') command ai=analoginput('nidaq','dev1'); %Use channel 0 (single ended input) of the defined analog input in_chan = addchannel(ai,0); %Set the input range of the channel: in_chan.inputrange = [-5,5]; %Setting up input parameters: %use set(ai) to see the parameters that can be set set(ai, 'Samplerate', 80E3); %Sample Rate of 50kHz set(ai, 'SamplesPerTrigger', 8E3); %Sample for.1 second set(ai, 'InputType', 'SingleEnded'); %Single ended input %Data collection: start(ai); [d_in, t] = getdata(ai); %stop([ai]); specified delete(ai); clear ai; fprintf('test 1 run\n'); plot(t,d_in) %Start data collection %store data in "d_in" and the time in "t" %end of test, not needed because sameples per trigger %delete test structure %clear analog input channel %plot the collected data [10.2] Shock Response Trial Code %Senior Design Team 165 %DAQ test with phase frequency detector and firing the solenoid %define input device as the NI-DAQ, its device ID is Dev1 %device ID determined through daqhwinfo('nidaq') command %while (q<.03) ai=analoginput('nidaq','dev1'); %Setting up input parameters: %run set(ai) to see the parameters that can be set set(ai, 'Samplerate', 80E3); %Sample Rate of 500kHz set(ai, 'SamplesPerTrigger', 1.2E4); %Sample for.15 seconds set(ai, 'InputType', 'SingleEnded'); %Single Ended input ai.channelskewmode = 'Equisample'; in_chan = addchannel(ai,0); in_chan.inputrange = [-5,5]; accel_channel = addchannel(ai,1); accel_channel.inputrange = [-5,5]; %Adds an input for the phase freq detector %Set the input range of the channel %Adds an input for the accelerometer %Set the input range of the channel

20 20 %Shock Pulse setup: a_out = zeros(1, floor(1*1e6)); %output array of length sample time*sample rate %Overwrites with ones at 1/10 of the way into sample time for the shock time: a_out(1,1:floor(.05*1e6)-1) = ones(1,floor(.05*1e6)-1); a_out = 5 * a_out; %sets the ones to the output of 5V0 %Setting up output channel: ao = analogoutput('nidaq', 'Dev1'); %Set output device out_chan = addchannel(ao, 0); %Select output channel set(ao, 'SampleRate', 1E6); %Define output sample rate putdata(ao, a_out'); %Output the 5V pulse defined above %Data collection: start([ai, ao]); [d_in, t] = getdata(ai); stop([ai,ao]); specified delete([ai,ao]); clear ai ao; fprintf('test 2 run\n'); %Start data collection %store data in "d_in" and the time in "t" %end of test, not needed because sameples per trigger %delete test structure %clear channels %run confirmation %Data Processing: [b,a] = butter(8,0.2); %butterworth lowpass filter definition inst_f = ((diff(d_in(:,1)*2*pi/4.552)./diff(t))/(2*pi)); %radian conversion and instantaneous frequency (Hz) calculation from phase data inst_f_filt = filtfilt(b,a,inst_f); %filtered instantaneous frequency [c,d] = butter(8,0.125); accel_filt = filtfilt(c,d,d_in(:,2)); %filtered accelerometer output inst_f_filt(1:500)=0; inst_f_filt = [0; inst_f_filt]; %Plots: figure(2) subplot(4,1,1), plot(t,d_in(:,1)), xlim([.03.07]), title('raw Phase Freq Detector') subplot(4,1,2), plot(t,d_in(:,2)), xlim([.03.07]), title('raw Accel Output') subplot(4,1,3), plot(t,accel_filt), xlim([.03.07]), title('filtered Accel Output') subplot(4,1,4), plot(t,inst_f_filt), xlim([.03.07]), title('filtered Inst. Freq.') %Store peaks: % choice = questdlg('is This Data Worth Saving?','Save It'); % switch choice % case 'Yes' % accel_peaks(i) = min(accel_filt); % freq_peaks(i) = min(inst_f_filt); % i=i+1; % q=q+.005; % break % case 'No' % disp('not Saving') % break % end % accel_peaks(i) = min(accel_filt); % freq_peaks(i) = min(inst_f_filt); % i=i+1; % q=q+.0005; % waitforbuttonpress; %end

21 21 [11] Project Collaborators: University of Connecticut Electrical Engineering Joseph Hiltz-Maher o Senior Design Team Member o University of Connecticut Electrical Engineering Major o Joseph.Hiltz-Maher@uconn.edu Max Madore o Senior Design Team Member o University of Connecticut Electrical Engineering Major o Max.Madore@uconn.edu Shalin Shah o Senior Design Team Member o University of Connecticut Electrical Engineering Major o Shalin.Shah@uconn.edu Shaun Hew o Senior Design Team Member o University of Connecticut Electrical Engineering Major o Shaun.Hew@uconn.edu Helena Silva, PhD o Faculty Advisor o HSilva@engr.uconn.edu Phonon Corporation Scott Kraft o Phonon Corporation Advisor o ScottK@phonon.com [12] Works Cited [1] Phonon Corporation. Phonon Corp. Web. 2 May < [2] Frerking, Marvin E. "Quartz Crystal Resonators." Crystal Oscillator Design and Temperature Compensation. New York: Van Nostrand, Print. [3] Vig, John R. "Quartz Crystal Resonators and Oscillators For Frequency Control and Timing Applications - A Tutorial." U.S. Army Communications-Electronics Command (2000). AM1 LLC. Web. 2 May < TUTORIAL.pdf>. [4] Himmel, J., R. McGowan, J. Kosinski, and T. Lukaszek. "Market Survey of Acceleration- Insensitive SAW Oscillators." Frequency Control Symposium, th., Proceedings of the 1992 IEEE (1992): IEEE. Web. 2 May <ieeexplore.ieee.org/xpls/abs_all.jsp?arnumber=269952>.

22 22 [5] McNair, Bruce. "Signal Generators and Waveform-Shaping Circuits." Lecture. Stevens Institute of Technology. Web. 2 May < [6] Phonon Corporation. "400 MHz Oscillator Data Sheet." 22 Aug Web. 3 May < [7] Frerking, Marvin E. "Oscillator Circuits." Crystal Oscillator Design and Temperature Compensation. New York: Van Nostrand, Print. [8] "Varactor / Varicap Diode Tutorial." Varactor / Varicap Diode. Radio-Electronics.com. Web. 02 May < [9] Moon, Sung Tae. "Introduction to RF VCO Design." Texas A&M University, Nov Web. 2 May < [10] Kosinski, John A., and Robert A. Pastore, Jr. "Theory and Design of Piezoelectric Resonators Immune to Acceleration: Present State of the Art." IEEE 48.5 (2001): Web. 14 Dec < mber=949753>. [11] EPCOS. Application Toolkit EPCOS SAW Resonators and Frontend Filters. EPCOS, Mouser. Web. 14 Dec < [12] Image of Phase Difference. Digital image. Wikipedia, 21 Feb Web. 2 May < Phase_shift.svg.png>. [13] "HMC439QS16G." Data Sheet Catalog. Hittite Microwave Corporation. Web. 2 May < [14] "How Do I Eliminate Ghosting From My Measurements?" National Instruments, 11 June Web. 2 May <

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