Improved PLL Tuning of Shunt Active Power Filter for Grid Connected Photo Voltaic Energy System

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1 Crcuts and Systems, 016, 7, Publshed Onlne August 016 n ScRes. Improved PLL Tunng of Shunt Actve Power Flter for Grd Connected Photo Voltac Energy System Rajmohan Rajalakshm 1, Varaman Rajasekaran 1 Department of Electrcal and Electroncs Engneerng, Combatore Insttute of Technology, Combatore, Inda Department of Electrcal and Electroncs Engneerng, PSNA College of Engneerng and Technology, Dndgul, Inda Receved 0 May 016; accepted 8 May 016; publshed 19 August 016 Copyrght 016 by authors and Scentfc Research Publshng Inc. Ths work s lcensed under the Creatve Commons Attrbuton Internatonal Lcense (CC BY). Abstract Ths research work brngs out the unque predctve current control method for attanng an effcent grd connected Photo Voltac (PV) system by Shunt Actve Power Flter (SAPF) as grd connected converter. The major objectve of the research work s to address the presence of Drect Current (DC) component, frequency mprovement, qucker theta response, voltage magntude estmaton n the nput sgnal of the Phase Locked Loop (PLL) whch s challengng. Ths work focuses on tunng the PLL block (K p, K, K v and K o) through Artfcal Bee Colony (ABC) optmzaton algorthm. The proposed ABC based modfed three-phase PLL method s based on addng a new loop nsde the PLL structure. In power converters, ABC algorthm s used to select the optmal swtchng states. The voltage vector whch mnmzes a cost optmzaton functon s selected. Smulaton s carred out for both balanced and unbalanced system and the results valdate that the performance of the proposed approach s better n terms of harmonc compensaton as per the IEEE standards wthn ±5%, power factor mprovement of the system, qucker theta trackng and suppresson of frequency jump wth the nterconnecton of PV system. Keywords Shunt Actve Flter, Phase Locked Loop, Artfcal Bee Colony, Current Control Method, PV System 1. Introducton In recent years, power qualty at end user s termnal s affected greatly and t has become a great concern n How to cte ths paper: Rajalakshm, R. and Rajasekaran, V. (016) Improved PLL Tunng of Shunt Actve Power Flter for Grd Connected Photo Voltac Energy System. Crcuts and Systems, 7,

2 R. Rajalakshm, V. Rajasekaran many ndustral applcatons. Therefore, t s very essental to dentfy novel and effcent system that would mtgate the dsturbances n the electrcal systems, mprovng ther power qualty [1]. Normal flters such as LC, LCL, etc., are used to elmnate specfed frequency range and thus, t can be only used for predetermned loads. Thus, Actve Power Flter (APF) has been used for these types of harmonc mtgaton concerns n transmsson lnes []. Shunt actve power flter has the growng popularty than seres actve power flter snce most of the ndustral applcatons requre the compensaton towards current harmoncs. It has the ablty to keep the current n the source as balanced and snusodal after compensaton, rrespectve of whether the load s nonlnear, balanced or unbalanced [3]-[5]. The utlzaton of SAPF provdes sgnfcant advantages to the power system. Thus, developng new methodologes have become an actve area of research to mprove the performance of these SAPFs [6]. In recent decades, nterconnecton of Renewable Energy Sources (RES) wth SAPF has become one of the attractve research topcs. But, there s a certan level of nfluence and mpact that renewable generaton has on power qualty on account of ts nonlnearty, especally as both solar generaton plants as well as wnd power generators have to be connected as such wth the grd usng hgh power statc Pulse Wdth Modulated (PWM) converters [7]. Power generaton n non unform nature has a drect effect on the voltage that s regulated theren and thus leads to voltage dstorton n power systems. Ths paper focuses on contrbutng an effcent compensaton technque to deal wth the problem of power qualty dsturbances n the power dstrbuton systems due to the RES nterconnecton. Many types of actve power flter confguratons have been proposed n the last two decades to acheve the requred harmonc compensaton level. The man technques n the actve flter are to generate the reference current and the control method appled to nject the requred compensaton current nto the lne, whch decdes the performance of an actve flter. There are several methods for reference current generaton for the shunt actve power flters. In 1984, H. Akag stated nstantaneous actve and reactve power theory control method that was qute effcent method for three phase loads n the balanced system, beng later worked by Watanabe and Aredes for three phase four wre systems; later F.Z. Peng proposed zero sequence currents. Synchronous Reference Frame (SRF) concept s smple algorthm havng good dynamc responses. The SRF could compensate the harmoncs n the current and reactve power component from the dstorted load currents. In 1995, Bhattacharya proposed dq component s calculatons of the nstantaneous three phase currents and created synchronous reference frame concept. A dq based current reference generator scheme s used to obtan the reference current sgnal of the actve power flter. Ths scheme presents a fast and accurate sgnal trackng capablty, whch avods voltage fluctuatons that deterorate the current reference sgnal affectng compensaton performance [8]. So, n ths work, dq based current reference generator scheme s preferred. To mplement the dq based current reference generator, some knd of synchronzng system should be used. PLL has been wdely used for the synchronzaton purpose. SRF-PLL has been wdely used n power system applcatons due to ts smplcty and consderable performance. But t suffers from double frequency error when the nput sgnal s unbalanced. Moreover, t also has drawbacks due to the presence of DC components. The DC component can be an ntrnsc component of a sgnal (e.g., the DC lnk voltage n a sngle phase rectfer that has a DC and a second order harmonc), and can be generated by measurement devces (e.g., due to the saturaton phenomenon n a current transformer [9]), converson processes (e.g., the A/D converson for fxed pont DSP applcatons [10]), or when a fault occurs [11]. Therefore, t s necessary to remove any error that such a component may cause. But, complete removal of DC component n the PLL systems has not been addressed n the lterature so far [1]. In ths paper the author proposed a method to address the DC component n the nput sgnal of the PLL and notch flter algorthms for flterng and synchronzaton applcatons. Ths paper takes the motvaton of the abovementoned work and focuses on mprovng the performance of the overall system through the utlzaton of swarm ntellgence optmzaton algorthm. Tradtonal PI controllers are wdely used n the control loop of the voltage source converters to produce the swtchng states of the converters because of ts smplcty n control desgn. Perfect tunng of the controller s needed to have the satsfactory operaton of the converters and several tradtonal tunng rules, such as Zegler and Nchols, Astrom and Hagglud, San and Ozgen cohen and coon etc. are adopted for ths purpose. Though they are enough for the frst order system, they produce large overshoot and requred repeated desgn process for any varatons n the system model. But n general the power system has many dsturbances, parameter vara- 3064

3 R. Rajalakshm, V. Rajasekaran tons and has many nonlnear loads whch lead to the degradaton of the qualty of the power. Hence the contnuous tunng algorthm s needed to have satsfactory operaton n ts dynamc nature [13]-[16]. Hence ths paper brngs out the unque optmzed self tunng of the controller for the PLL structure n the current control loop of the VSCs, whch s obtaned by ABC algorthm. The man contrbuton of ths paper s to tune the PLL block parameters such as proportonal gan (K p ), ntegral gan (K ), change n the nstantaneous frequency (K o ) and voltage magntude gan (K v ). The settlng tme and the steady state response of the frequency are tuned by K and K p gan values. Smlarly, elmnaton of DC component and dentfcaton of the voltage magntude are tuned through K o and K v gan values through the ABC optmzaton approach. Moreover, the control loop of Voltage Source Inverter (VSI) s proposed wth the predctve current control approach. Ths method predcts the future load current values for the voltage vectors generated by the nverter. The voltage vector whch mnmzes a cost optmzaton functon s selected. The cost optmzaton functon used n ths work evaluates the error current at the next samplng tme. In order to select the optmal swtchng state that must be appled to the power converter, ABC optmzaton s used n ths work whch selects the best mnmal optmal value g. Ths paper s organzed as follows. Secton deals wth the proposed methodology. Secton 3 dscusses about the three leg converter model. Secton 4 descrbes about the proposed ABC based predctve current control model. Secton 5 narrates about current reference generaton. Secton 6 valdates the smulaton results to proof the performance of the proposed system.. Proposed Methodology Fgure 1 shows the proposed SAPF system model wth RES nterconnecton. The electrcal energy consumpton behavour s an unpredctable, and random n nature. It may be sngle or three-phase, balanced or unbalanced, and lnear or nonlnear. A shunt actve power flter s connected at the pont of common couplng n parallel to compensate current harmoncs, current unbalance, and reactve power [17]. As shown n Fgure 1, t s composed by an electrolytc capactor, a PWM converter and a frst order output rpple flter. Ths crcut utlzes the power system equvalent mpedance Z s, output rpple flter mpedance Z f of the converter and the mpedance Z L of the load. When RES generates excess power than the load demand, then the excess power s gven to the grd to mantan the load voltage of frequency constant. Fgure 1. Shunt actve power flter model. 3065

4 R. Rajalakshm, V. Rajasekaran The man element of ths system s a voltage source nverter, as t nterfaces the renewable energy source to the grd and delvers the generated power. In ths work, grd nterfacng nverter can effectvely be utlzed to perform the followng mportant functons: 1) non lnear load current harmoncs mtgaton; ) unbalanced current compensaton n case of 3 phase 3 wre system; 3) ABC based Predctve control technque for cost optmzaton 4) ABC based PLL tunng approach under unbalanced load condtons. Moreover, wth adequate control of grd nterfacng nverter, all the four objectves can be accomplshed ether ndvdually or smultaneously. 3. Three Leg Converter Model An llustraton of converter s power crcut employed here s presented n Fgure. Converter topology has smlar features to those of tradtonally deployed three phase converter that has a three leg system [18]. The swtchng states of the converter are decded by the gatng sgnals S u, S v and S w, as follows n Equaton (1): 1 f S1 ON and S OFF Su = 0 f S1 OFF and S ON 1 f S ON and S5 OFF Sv = 0 f S OFF and S5 ON 1 f S3 ON and S6 OFF Sw = 0 f S3 OFF and S6 ON and Equaton (1) can be expressed n vectoral form as n Equaton (). S = S + as + a S ( ) 3 u v w (1) () jπ where 3 a = e. The output voltage space vectors created by the nverter are defned as n Equaton (3) v = 3 ( vun + avvn + a vwn) (3) Fgure. Three leg nverter. 3066

5 R. Rajalakshm, V. Rajasekaran where vun + avvn + a vwn are the phase to neutral (N) voltages of the nverter (Fgure ). Then, the load voltage vector can be related to the swtchng state vector S as n Equaton (4) v = V S (4) where V dc s the DC lnk voltage. Takng n to consderaton gatng sgnals combnatons of S u, S v and S w eght swtchng states, and as a result, eght voltage vectors are thus obtaned. Note that vo = v7, whch results n only seven dfferent voltage vectors, as shown n Fgure 3. Flter s mathematcal model dervaton s gven n Equaton (5). do vo = v Req0 Leq (5) dt where R eq and L eq are the 3L-VSI output parameters expressed as Thevenn mpedances at the converter output termnals Z eq. Hence, the Thevenn s equvalent mpedance s calculated by a seres connecton of the rpple flter mpedance Z f and the arrangement n parallel between the system equvalent mpedance Z s and the load mpedance Z L as shown n Equaton (6). Z dc ZZ = S L eq ZS + Z + L For ths model, t s assumed that ZL ZS, and the resstve part of the system s equvalent mpedance s neglected, and the seres reactance s consdered n the range of 3% - 7% p.u., whch s a satsfactory approxmaton of the real system. Fnally, n Equaton (5) R eq = R f and L eq = L s + L f. For complete understandng the PWM swtchng tme calculaton of the nverter swtches are gven n Table 1. Table 1. Swtchng tme calculaton of the nverter. Z f (6) Sector Swtchng tme vector S = T + T + T S = T + T 0 s ( 0.5 T ) = 3 0 S = T + T S = T + T + T 1 0 s ( 0.5 T ) = 3 0 S = T + T S = T + T + T 1 0 s = T + T 3 0 ( 0.5 T ) s = 1 0 S = T + T + T 1 0 S = T + T s = T + T 1 0 S ( 0.5 T ) = 0 S = T + T + T s = T + T + T S ( 0.5 T ) = 0 S = T + T

6 R. Rajalakshm, V. Rajasekaran Fgure 3. Voltage vector generated by the nverter Desgn of DC Lnk Capactor The value of dc lnk capactor s chosen from the reference dc voltage, ( V dlnk max ) s the maxmum voltage level of the dc bus, I s the phase current of VSI, ω s the angular frequency and (t) tme for whch dc bus voltage s to be recovered. It s gven as n Equaton (7). C dc = π I c ( rated) 3 ωt V dlnk max where ω = π 50 = ; I c(rated) = rated current, Vdlnk max = 700 V 3.. Desgn of Flter Inductance The amount of flterng nductance to be added to the SAPF s L V dlnk f = (8) rp peak fsw max ( I ) where ( V dlnk ) represents dc lnk voltage, ( fsw max ) represents maxmum swtchng frequency, ( I ) represents peak to peak rpple current. V rp peak dlnk = 700 V, I = 11.6 Amps, fsw max = Hz = 30 khz. 4. Predctve Current Control rp peak Fgure 4 shows the block dagram of the proposed predctve current control scheme. Predctve control s characterzed by ts system model usage that helps n predctng varables for future behavour that necesstates controllng. Controller utlzes the partcular nformaton n order to choose the optmum swtchng state whch n turn wll be appled to the power converter, as per predefned optmzaton decsve factors Current Reference Generator It s derved and desgned so that the requred current reference may be generated and the same may be utlzed for compensatng any undesrable load current components. Wth respect to ths one, system voltages, DC lnk voltage of converter as well as the load currents are measured. Durng the unbalanced current/voltage condtons, PLL tunng s requred. But, n order to mprove the conventonal PLL tunng, an ntellgent ABC optmzaton algorthm s used n ths approach 4.. Predctve Model Usng ABC Converter model s employed for predcton of output current of the converter. Implyng that consderng a gven samplng tme T s, dentfyng converter swtchng states and control varables at nstant kt s, predcton of next states s feasble at any nstant ( k + 1) T s. On account of frst order nature that s nherent n state Equatons (3-6) that ental detals of the model, a relatvely accurate frst order approxmaton of the dervatve has been taken n to consderaton here as n Equaton (9). ( + 1) x( k) dx x k (9) dt T s (7) 3068

7 R. Rajalakshm, V. Rajasekaran Fgure 4. Proposed ABC based predctve current control scheme Proposed ABC Algorthms for Optmal Swtchng of the Converter In [19] the authors proposed the Artfcal Bee Colony algorthm wheren each of the colones comprses of three groups the employed, the onlookers and the scouts. A random swtchng state ( V1,, V8) s ntalzed and each soluton vector s generated. Then, each employed bee found new sources whose quantty s equal to half of the total sources. The man purpose for determnng the new food source s evaluaton of nectar amount and subsequently greedy selecton s carred out. In ABC, both employed and onlooker contrbute as beng part of the operaton and scouts carry out exploraton. Bees am at maxmzng food quantty brought back nto the nest. Step 1: Generate the ntal swtchng state V, where = 0,1,,, 7 Step : Calculate the voltage for each swtchng state (partcle) to obtan output voltage for each swtchng state V (P ), and select the best θ k ( c) as P. Evaluate the ftness (output voltage for each swtchng state) (f = P ) of the swtchng state Step 3: Use the teraton formulae of ABC to get a new routng path. For each employed bee Do Produce new soluton X of swtchng state of the nverter Calculate the value f of swtchng state of the nverter Apply greedy selecton process Calculate the probablty values P for the solutons V For each onlooker bee Select a soluton V dependng on P Produce new soluton X Calculate the values f Apply greedy selecton process If there s a dscarded soluton for the scout then replace t wth a new soluton whch wll be randomly produced. Memorze the best soluton so far. The algorthm terates to the preferred cycle number and the sources havng the best nectar n mnd gves the possble values of the varables. The obtaned nectar amount denotes the soluton of the objectve functon. The 8 possble output current predcted values can be obtaned as n Equaton (10) T ReqT s s o[ k + 1] = ( v[ k] vo[ k] ) [ k] (10) L eq L eq As shown n Equaton (10), n order to predct the output current o at the nstant [ k + 1], the nput voltage value v and the converter output voltage v o are requred. The algorthm calculates all 8 values assocated wth the possble combnatons that the state varables can acheve. 3069

8 R. Rajalakshm, V. Rajasekaran 4.4. Cost Functon Optmzaton Selecton of optmal swtchng state applcable to power converter requres, comparson of 8 predcted values k + 1 wth reference by deployng a cost functon g, as follows n Equaton (11). obtaned for [ ] o Here [ 1] * * * ( ou ou ) ( ov [ ] ov [ ]) ( ow [ ] ow [ ]) [ ] [ ] [ ] g k + 1 = k + 1 k k + 1 k k + 1 k + 1 (11) oa ob oc g k + represents the error dfference between the actual flter currents, and and the reference flter currents *, * and * oa ob oc. The output current o s equal to the reference current * o when g = 0. Therefore, the man goal of the cost optmzaton s to acheve the g value close to zero. Voltage vector v N s selected as t reduces cost functon and applcable for subsequent samplng state. Through each samplng state, swtchng state generatng mnmum value of g s chosen amongst 8 probable functon values. Algorthm chooses that swtchng state whch generates mnmal value and then the same s applcable to the converter durng the [ k + 1] state. An accurate and fast detecton of the theta and frequency s essental to assure the correct generaton of the reference sgnals. So, n ths work, ABC optmzaton s used n PLL to optmze ts parameters ( Kp, K, Kv and K o) to obtan better steady state response, settlng tme, voltage magntude and DC component elmnaton. 5. Current Reference Generaton DQ based reference current generaton scheme has been employed here to attan actve power flter current reference sgnals. The scheme offers quck and precse sgnal trackng capabltes. Ths partcular feature negates voltage fluctuatons deteroratng reference current sgnal that nfluence compensaton performance [8]. Fgure 5 shows how reference current sgnals are attaned through matchng load currents. Ths module calculates the necessary reference current sgnals for the converter so as to compensate reactve power, current harmonc & sn and the maxmum Total Harmonc current mbalance respectvely. The dsplacement power factor ( ( L )) Fgure 5. dq based reference current generator. 3070

9 R. Rajalakshm, V. Rajasekaran Dstorton (THD) of the load THD L defnes the relatonshps between the apparent power needed by the actve power flter, wth related to the load, as shown n Equaton (1) S S APF L = sn + THD L 1+ THD where the value of THD L ncludes the maxmum compensable harmonc current, defned as double the samplng frequency f s. The frequency of the maxmum current harmonc component to be compensated s equal to one half of the converter swtchng frequency. DQ based scheme s operatonal as part of the rotatng reference structure, hence measured currents need to be multpled usng snω t and cosω t sgnals. Deployment of dq transformaton, d current component synchronzaton needs to be done wth respect to correspondng phase to neutral system voltage; q current component s phase shfted by 90. Obtanng snω t and cosω t synchronzed reference sgnals are done usng SRF-PLL [0]. A pure snusodal waveform s generated by the SRF-PLL when there s severe dstorton n system voltage. Elmnatng of trackng errors s feasble as SRF-PLLs are desgned so that phase voltage unbalancng s evaded, harmoncs (.e., less than 5% and 3% n ffth and seventh, respectvely) and resultant offset generated on account of nonlnear load condtons and measurement errors. Thus, for the complete removal of DC component and sudden response of frequency ABC s used n ths work to tune the PLL block ( Kp, K, Kv and K o). The settlng tme and the steady state response of the frequency are tuned by K and K p gan values. Smlarly, elmnaton of DC component and dentfyng the voltage magntude are tuned through K o and K v gan values through the ABC optmzaton approach. Equaton (13) shows the relatonshp between the real currents Lx ( t ) where x= uv, and w and the assocated dq components ( d and ) s q Lu d snωt cosωt Lv = q 3 cosωt snωt 3 3 (13) 0 Lw The DC component of the phase currents d s extracted by a Low Pass Flter (LPF) to generate the harmonc reference components d. The correspondng Alternatng Current (AC) and DC components of are q phase shfted by 180 to obtan the reference components (reactve) of the phase currents. Mantanng DC voltage constant, the ampltude of the converter reference current should be modfed by addng an actve power reference sgnal wth the d component dscussed below. The resultng sgnals * * c d and q are transformed as three phase sgnals by applyng the nverse Park and Clark transformaton, as shown n Equaton (14). In ths paper the cut off frequency of the LPF s used as 0 Hz * ou o * * ov 0 snωt cosωt = d * 3 (14) * ow 0 cosωt snωt q A sgnfcant advantages that dq based current reference generator scheme offers s that t facltates a lnear controller mplementaton n DC voltage control loop. Though, an obvous dsadvantage that arses from dq based current reference frame algorthm, deployment for producng reference current generaton s of second order harmonc components n d and q n an unbalanced operatng state. Harmoncs ampltude s based on the unbalanced load current percentage expressed as the relatonshp between the postve sequence current L1 and the negatve sequence current L. Tradtonally PI controller s used to control the DC voltage of the converter. Ths s an mportant ssue n the evaluaton, snce the cost functon accordng to the Equaton (9) s desgned usng only reference currents, n order L L (1) 3071

10 R. Rajalakshm, V. Rajasekaran to avod the use of weghtng factors. In general, these weghtng factors are obtaned expermentally, and they are not well defned for dfferent operatng condtons. In addton to that, the slow dynamc response of the voltage across the electrolytc capactor wll not affect the current transent response. For ths reason, the PI controller represents a smple and successful way for the DC voltage control. The DC voltage remans constant (wth a mnmum value of ( 6v s ( rms )) untl the actve power absorbed by the converter decreases to a level of the nablty to compensate t s losses. The absorbed actve power by the converter s controlled by adjustng the ampltude of the actve power reference sgnal c, whch s n phase wth each phase voltage. In the block dagram shown n Fgure 6, the DC * voltage v dc s measured and then compared wth a constant reference value v dc. The error (e) s processed by a PI controller, wth two gans, K and p K. Fgure 6 shows that the output of the PI controller s gven to the DC voltage transfer functon G s, whch s represented by a frst order system are brefly explaned n [1]. In the conventonal tunng of PLL there s a frequency jump n the grd voltage and a delay n theta trackng. Both wll be vares wth respect to the type of load used. Moreover the varyng nature of RES produces rpples n the output whch affects the grd voltage [] [3], whch s gven to PLL as feedback here. Ths wll affect the njecton tme of the compensatng current nto the grd. To avod these demerts n ths paper the conventonal method of tunng s replaced by ABC based tunng to enhance the performance of the overall system Modfed Three-Phase PLL to Avod DC Error For a three phase balanced set of nput sgnals s as shown n the Equaton (15) π π vabc = V sn ( θ), V sn θ, V sn θ and the d component s gven as n the Equaton (16) d sn ( ) T (15) V = V θ ϕ (16) The loop regulates ths quantty to zero and, thus, regulates φ to θ. Assume that the nput sgnal has a DC component of ( d,, ) T a db d c ; then, a term as shown n Equaton (17) wll supermpose on v d. If the DC offset s unbalanced (.e., has unequal values on three phases), ths causes an error whose frequency s the same as (17) π π 3 da cosϕ + db cos ϕ + dc cos ϕ fundamental frequency. The proposed ABC based modfed three phase PLL s shown n Fgure 7. Here the block T denoted by dot makes the dot product of ts nputs: xy, = xy It s to be observed that the output of ths block 3 s equal to V d. Thus, the factor /3 s placed to make t equal to V d. 5.. Objectve Functon for Tunng PLL Usng ABC Algorthm Ths secton dscusses about the tunng of gan values to attan the optmal performance of PLL. K value depends on the frequency factor ω, K gan value depends on the angle. The voltage magntude s based on the p K v gan value where as the K o gan value depends on the DC component. The objectve functon of ths approach would be to mnmze the THD and Settlng Tme ST of the proposed model n Fgure 8 as follows. Fgure 6. DC voltage control block dagram. 307

11 R. Rajalakshm, V. Rajasekaran Fgure 7. ABC based modfed three-phase PLL to avod DC error. Fgure 8. Mnmum cost functon evaluaton. ( p v d o) 1 + Mnmze f K, K, K an K = w THD w ST (18) where w 1 and w are the parameters for calbraton. The parameters subjected to lmt, consdered n ths research work are Kp < K mn p < Kp max K < K mn < K max Kv < K mn v < Kv (19) max Ko < K mn o < Ko max Sat < Sat < Sat mn Manual tunng of the controller parameters n removng the performance becomes more dffcult and consumes more tme. To overcome ths major drawback, ABC based optmzaton approach s proposed here to auto tune the controller parameters and also to mprove the effcency of the control strategy n extractng reference currents for SAPF under non lnear load condtons also. max 3073

12 R. Rajalakshm, V. Rajasekaran 5.3. Workng of the Proposed ABC based PI Self Tunng 1) Intalze the populaton ( v abc ) of solutons ) Intally, the controller parameter are generated whch s of sze N 3) Produce new solutons of DC components through employed bees and then apply greedy selecton process 4) Probablty values are calculated for the above soluton 5) Produces new set of populaton for the parameters of the controller 6) Update the best values acheved so far, and sort the obtaned values 7) Based on probablty values agan the new solutons are obtaned through onlooker bees and then apply greedy selecton process 8) Determne the left out soluton for the scout, f exsts, and replace t wth a new randomly produced soluton 9) Update the best value acheved so far The proposed structure of Fgure 7 the DC component n the nput sgnal s detected by the branch comprses three ntegrators wth equal gans K o to estmate the DC components on three phases. Snce the DC components are estmated by ths branch and added to the output, the sgnal e wll have no DC. Thus the error n the whole loop s elmnated by removng the DC component, whch assures the PLL operaton no longer suffers from such components. The modfed PLL equatons are gven n Equaton (0). V = µ 1esn, ω = µ ecos (0) = µ 3ecos + ω, d = µ oe where e= v d V sn. The varables V, ω and estmate voltage magntude, frequency and angle of the nput sgnal wth nomnal fundamental frequency of ω o. Thus t s observed that, besdes THD and Settlng Tme of the DC lnk voltage TV, the work also concentrates on choosng the optmal flter current wth a mnmum cost functon. dc 6. Smulaton Results and Evaluaton Ths work has been smulated n MATLAB SIMULINK r011a. Ths secton clearly dscusses about the performance evaluaton of the proposed model n whch the voltage source converter s controlled to acheve mnmzed current harmoncs under non lnear load condtons at unty power factor. Moreover, ths proposed model s verfed for the RES nterconnecton wth nverter to attan balanced snusodal grd currents under unbalanced load condtons through ABC optmzaton technque. The other smulaton scenaro wheren the PLL s tuned to elmnate DC component, mnmzng the peak overshoot and mprovng the settlng tme of frequency and theta s consdered. In ths smulaton, the V represents grd voltage, grd I represents grd current, grd I Load represents the load current, I nv represents the nverter current and V dc represents DC lnk voltage System Behavor wth SAPF for Nonlnear Load under Balanced Condton The nonlnear behavor of the three phase grd system wth nonlnear balanced load condton and how the compensaton s done wth the help of the voltage source converter actng as SAPF for the grd connected PV system s clearly depcted n Fgure 9. Fgure 9(a) shows the grd voltage profle wth the magntude of 35 V, taken between lne to ground for all the three phases. Here for the analyss a three phase dode brdge rectfer feedng resstve load s consdered as nonlnear load throughout the smulaton dscusson. Due to ths nonlnear load, the snusodal nature of the grd current s affected as shown n Fgure 9(b) up to 0. seconds. The nonlnear dode brdge rectfer wll draw a nonlnear load current as shown n Fgure 9(c). The effect of the SAPF on the grd current, load current and the DC lnk voltage s recognzed from 0. seconds, snce the converter starts to nject the compensatng current, actng as SAPF from that moment as shown n Fgure 9(d). Now the compensatng performance of the SAPF could be clearly understood from Fgure 9(e) and Fgure 9(f). For the clarty of understandng the current waveform s shown for phase A alone n Fgure 9(e). The source current compensaton could also be seen n Fgure 9(b) after 0. seconds. The DC lnk grd voltage has rsng nature up to 0. seconds and after the njecton of compensatng current, t s quckly forced to be mantaned at 680 V as per the system desgn and the steady state nature could also be realzed from Fgure 9(f). 3074

13 R. Rajalakshm, V. Rajasekaran (a) (b) (c) (d) (e) (f) Fgure 9. (a) Grd voltage; (b) Grd current; (c) Nonlnear load current; (d) Inverter current; (e) Load current vs source current; (f) DC lnk voltage. 3075

14 R. Rajalakshm, V. Rajasekaran 6.. System Behavor wth SAPF for Nonlnear Load under Unbalanced Condton The performance of the ABC tuned SAPF for both nonlnear and unbalanced load condtons could be apprecated by analysng the waveforms shown n Fgure 10. Here the unbalanced condton s consdered from 0. seconds onwards and up to that the system operates the nonlnear load under balanced condton only. Load unbalancng s created at 0. seconds, only on two phases.e., phase A and phase B havng 0A as unbalanced load currents. Phase C s kept n balanced nonlnear condton wth the current magntude of 14 A. Ths s shown n Fgure 10(a). Fgure 10(b) llustrates the compensatng current generated by the SAPF whch s to be njected nto the grd for reducng harmoncs and mantanng the balanced condton of the system. Tll 0. seconds the system has nonlnearty alone as shown n Fgure 10(a). Ths nonlnear nature of the grd current for balanced condton s compensated by the proposed SAPF model to reduce the harmonc currents. After 0. seconds the SAPF s producng the compensatng current to compensate the harmonc current as well as to make the system as balanced one. The performance of the proposed model for the unbalanced nonlnear system s evaluated by nvestgatng the waveform shown n Fgure 10(c). Tll 0. seconds the proposed model njects the compensatng current waveform and thus makng the grd current as snusodal one for the balanced system. The unbalanced system whch s created at 0. seconds has become as a balanced lnear system by drawng the current as 18 A n each phase approxmately due to the optmal reference current generator Performance Evaluaton of Proposed ABC Tuned and Conventonal PLL The man objectve of ths paper whch s known as ABC tuned PLL wth predctve current control method of SAPF s for optmzng the control parameters of the PLL can be evaluated by comparng t wth the conventonal PLL model, based on the factors frequency response, theta trackng, elmnaton of DC component and mantan the voltage magntude of the system. Fgure 11 shows the evdence for the better performance of the proposed PLL model compared to the conventonal model. (a) (b) (c) Fgure 10. (a) Unbalanced nonlnear load current; (b) Inverter current for unbalanced load; (c). Grd current for unbalanced load. 3076

15 R. Rajalakshm, V. Rajasekaran Fgure 11(a) compares the frequency response of the proposed model wth the conventonal model n tunng the PLL. It s clearly shown that the proposed model results n lesser peak overshoot and qucker settlng tme of the system frequency at 50 Hz. Moreover t holds good even under unbalanced load condtons. It could also be realzed from the same fgure at 0. seconds, at whch the unbalancng s created n the system. Improvng the frequency response s taken care by the proper tunng of the PLL parameter K. Fgure 11(b) compares the theta trackng response of the proposed model wth the conventonal model. It s clearly understood that the proposed ABC tuned PLL tracks the theta quckly even from 0.01 seconds where as t s hgher for the conventonal model of the PLL. The qucker theta trackng nfluences the generaton of reference current, selectng the optmal swtchng of the converter and thus mprovng the harmonc compensaton. By the proper tunng of K gan value, good response n trackng the theta value could be done. p Fgure 11(c) shows the voltage DC component response of proposed ABC tuned PLL and the conventonal SRF-PLL. The DC component may be naturally present n the nput sgnal or may be generated due to nonlnear/unbalanced load condtons. Ths DC component creates low frequency oscllatons that cannot be removed usng conventonal flterng technques as t may degrade the overall performance of the system and thus an effcent PLL structure s essental. Now, n order to attan almost zero DC components, an effcent ABC optmzaton loop s ntegrated nsde the PLL structure whch results n effectve elmnaton of the DC component by tunng the K o gan value. The optmal voltage magntude response s attaned by tunng the K v gan value as shown n Fgure 11(d). Wth optmal tunng of K v gan value, lesser peak overshoot response s acheved n the proposed model and hence the quck settlng and the mproved magntude response of the three phase system voltage wth the fundamental frequency s as shown n Fgure 11(e) n per unt value. Obtanng zero error n the comparson of v f abc and v abc as shown n Fgure 11(f) ncreases the overall performance of the PLL and thus mprovng the performance of the proposed SAPF model for the nterconnected PV system to the grd. The power factor of the grd system s nearest to unty as shown n Fgure 11(g) THD Analyss of the System Table shows the harmonc analyss of the waveforms for the system wthout SAPF, wth conventonal SAPF and wth the modfed SAPF. It gves the THD value of the harmonc current of the system for the each case n balanced and unbalanced load condtons. It gves the THD comparson for the system under varous harmonc orders. 7. Concluson The desgn of ABC based PLL tuned SAPF has been proposed n ths paper for a grd connected solar PV system. The dynamc performance of the proposed model n compensatng current harmoncs and reactve power consumpton s evaluated through the Matlab smulaton. In ths research, ABC optmzaton s proposed to select the optmal swtchng states that must be appled to the power converter, by selectng the best mnmal optmal Table. Analyss of % THD for the nonlnear load under balanced and unbalanced condton. Grd current THD n % for nonlnear load at balanced condton Method 5 th 7 th 9 th 11 th 13 th 15 th 17 th THD SRF-PLL based SAPF (Conventonal) ABC based PLL tunng of SAPF (Proposed) Grd current THD n % for nonlnear load at Unbalanced condton SRF-PLL based SAPF (Conventonal) ABC based PLL tunng of SAPF (Proposed) Note : In both cases nonlnear load current (wthout SAPF) %THD =

16 R. Rajalakshm, V. Rajasekaran (a) (b) (c) (d) (e) (f) 3078

17 R. Rajalakshm, V. Rajasekaran (g) Fgure 11. (a) Frequency response; (b) Theta response; (c) DC component; (d) Voltage magntude; (e) Grd voltage (pu); (f) Dc error; (g) Phase sequence of the grd voltage and grd current. value g. Smulated results have proved that the proposed predctve control algorthm s a good choce to classcal lnear control methods and the compensaton effectveness of the proposed shunt actve power flter wth ABC based PLL tunng. The performance of the proposed approach has been evaluated under unbalanced load condtons and t s observed that the proposed modfed PLL approach attans fast theta trackng as 0.15 seconds, quck settlement of frequency compared wth ±0. Hz jumpng of conventonal model, mantanng of the DC voltage magntude n 700 V wthn 0.4 seconds, zero error for the presence of DC component, mproved settlng tme and mnmal attanment of THD as 1.% for balanced load and 3.79% for unbalanced load. In the future the work can be extended to mprove the voltage qualty of the system and the converter operaton can be analyzed as a smple nverter for njectng the power derved from solar PV and as SAPF for current harmonc compensaton. Instead of VSI, multlevel nverters may be used for harmonc reducton. References [1] Fuchs, E.F., Roesler, D.J. and Kovacs, K.P. (1987) Senstvty of Electrcal Applances to Harmoncs and Fractonal Harmoncs of the Power System s Voltage. Part II: Televson Sets, Inducton Watt-Hour Meters and Unversal Machnes. IEEE Transacton on Power Delvery,, [] Pnto, J.G., Neves, P., Gonçalves, D. and Afonso, J.L. (009) Feld Results on Developed Three Phase Four Wre Shunt Actve Power Flters. 35th Annual Conference of IEEE Industral Electroncs, Porto, 3-5 November 009, [3] Salam, Z., Cheng, T.P. and Jusoh, A. (006) Harmoncs Mtgaton Usng Actve Power Flter: A Technologcal Revew. ELEKTRIKA, 8, [4] Mahapatra, K.K., Ghosh, A. and Doradla, S.R. (1998) Smplfed Model for Control Desgn of STATCOM Usng Three Level Inverter. IEEE Regon 10 Internatonal Conference on Global Connectvty n Energy, Computer, Communcaton and Control, Vol., [5] Rahman, S., Mendalek, N. and AlHaddad, K. (010) Expermental Desgn of a Nonlnear Control Technque for Three Phase Shunt Actve Power Flter. IEEE Transacton on Industral Electroncs, 57, [6] Akag, H. (1996) New Trends n Actve Flter for Power Condtonng. IEEE Transacton on Industral Applcatons, 3, [7] Rocabert, J., Luna, A., Blaabjerg, F. and Rodríguez, P. (01) Control of Power Converters n AC Mcrogrds. IEEE Transacton on Power Electroncs, 7, [8] Montero, M.I.M., Cadaval, E.R. and Gonzalez, F.B. (007) Comparson of Control Strateges for Shunt Actve Power Flters n Three-Phase Four Wre Systems. IEEE Transacton on Power Electroncs,, [9] Nam, S.-R., Park, J.-Y., Kang, S.-H. and Kezunovc, M. (009) Phasor Estmaton n the Presence of DC Offset and CT Saturaton. IEEE Transacton on Power Delvery, 4, [10] Cobotaru, M., Teodorescu, R. and Agelds, V.G. (008) Offset Rejecton for PLL Based Synchronzaton n Grd Connected Converters. 3rd Annual IEEE Applcatons of Power Electroncs Conference and Exposton, Austn, 4-8 February [11] Strnger, N.T. (1998) The Effect of DC Offset on Current Operated Relays. IEEE Transactons on Industral Applcatons, 34, [1] Gharteman, M.K., Khajehoddn, S.A., Jan, P.K., Bakhsha, A. and Mojr, M. (01) Addressng DC Component n 3079

18 R. Rajalakshm, V. Rajasekaran PLL and Notch Flter Algorthms. IEEE Transactons on Power Electroncs, 7, [13] Baslo, J.C. and Matos, S.R. (00) Desgn of PI and PID Controllers wth Transent Performance Specfcaton. IEEE Transactons on Educaton, 45, [14] Abdennour, A. and Alturk, F.A. (008) A Comparatve Study of PI/PID Classcal and Intellgent Tunng Methods. Journal of Engneerng and Computer Scences, 1, 9-4. [15] Cheng, M., Sun, Q. and Zhou, E. (006) New Self Tunng Fuzzy PI Control of a Novel Doubly Salent Permanent Magnet Motor Drve. IEEE Transacton on Industral Electroncs, 53, [16] Khorramabad, S.S. and Bakhsha, A. (014) Crtc Based Self Tunng PI Structure for Actve and Reactve Power Control of VSCs n Mcrogrd System. IEEE Transacton on Smart Grd, 6, [17] De Araujo Rbero, R.L., de Azevedo, C.C. and de Sousa, R.M. (01) A Robust Adaptve Control Strategy of Actve Power Flters for Power Factor Correcton, Harmonc Compensaton and Balancng of Nonlnear Loads. IEEE Transacton on Power Electroncs, 7, [18] Rodrguez, J., Pontt, J., Slva, C.A., Correa, P., Lezana, P., Cortés, P. and Ammann, U. (007) Predctve Current Control of a Voltage Source Inverter. IEEE Transactons on Industral Electroncs, 54, [19] Karaboga, D. and Ozturk, C. (011) A Novel Clusterng Approach: Artfcal Bee Colony (ABC) Algorthm. Appled Soft Computng, 11, [0] Chung, S.-K. (000) A Phase Trackng System for Three Phase Utlty Interface Inverters. IEEE Transacton on Power Electroncs, 15, [1] Acuna, P., Moran, L., Rvera, M., Dxon, J. and Rodrguez, J. (014) Improved Actve Power Flter Performance for Renewable Power Generaton Systems. IEEE Transactons on Power Electroncs, 9, [] Reddy, N.J., Kalamoorthy, M. and Ashok, K.D. (008) Control of Grd Connected PV Cell Dstrbuted Generaton Systems. TENCON IEEE Regon 10 Conference, Hyderabad, 19-1 November 008, [3] Mylsamy, K., Varaman, R., Irudayaraj, G.C.R. and Lawrence, H.T.R. (014) Expermental Valdaton of a Cascaded Sngle Phase H-Brdge Inverter wth a Smplfed Swtchng Algorthm. Journal of Power Electroncs, 14, Submt or recommend next manuscrpt to SCIRP and we wll provde best servce for you: Acceptng pre-submsson nqures through Emal, Facebook, LnkedIn, Twtter, etc. A wde selecton of journals (nclusve of 9 subjects, more than 00 journals) Provdng 4-hour hgh-qualty servce User-frendly onlne submsson system Far and swft peer-revew system Effcent typesettng and proofreadng procedure Dsplay of the result of downloads and vsts, as well as the number of cted artcles Maxmum dssemnaton of your research work Submt your manuscrpt at:

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