Experimental demonstration of 10 Gb/s multilevel carrier-less amplitude and phase modulation for short range optical communication systems
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1 Experimenal demonsraion of 1 Gb/s mulilevel carrier-less ampliude and phase modulaion for shor range opical communicaion sysems Li Tao, 1,2 Yiguang Wang, 1 Yuliang Gao, 3 Alan Pak Tao Lau, 3 Nan Chi, 1,* and Chao Lu 2 1 Deparmen of Communicaion Science and Engineering, and Sae Key Lab of ASIC & Sysem, Fudan Universiy, Shanghai 2433, China 2 Phoonics Research Cener, Deparmen of Elecronic and Informaion Engineering, The Hong Kong Polyechnic Universiy, Hong Kong 3 Phoonics Research Cener, Deparmen of Elecrical Engineering, The Hong Kong Polyechnic Universiy, Hong Kong * nanchi@fudan.edu.com Absrac: Carrier-less ampliude and phase (CAP) modulaion can be a good candidae for shor range opical communicaions for considerable compuaional complexiy reducion and simple sysem srucure. In his paper, a deailed invesigaion on he digial filers in CAP modulaion sysem is presened. An adapive equalizer based on cascaded mulimodulus algorihm (CMMA) is used for he demodulaion a he receiver. The impac of digial filer aps on sysem performance is invesigaed hrough comprehensive simulaions and a 1 Gb/s CAP16 modulaion sysem is demonsraed experimenally. The BER performance for differen lengh of fiber link is measured. Compared wih back-o-back (BTB) ransmissions, 2 db and 3.5 db receiver power penaly are observed a BER of 1 3 for 2 km and 4 km fiber link respecively. I clearly demonsraes he feasibiliy of he CAP16 modulaion for he shor range ransmission sysems. 213 Opical Sociey of America OCIS codes: (66) Fiber opics and opical communicaions; (6.48) Modulaion. References and links 1. G. K. Chang, A. Chowdhury, Z. Jia, H. C. Chien, M. F. Huang, J. Yu, and G. Ellinas, Key echnologies of WDM-PON for fuure converged opical broadband access neworks, J. Op. Commun. New. 1(4), C35 C5 (29). 2. J. L. Wei, J. D. Ingham, D. G. Cunningham, R. V. Peny, and I. H. Whie, Comparisons beween 28 Gb/s NRZ, PAM, CAP and opical OFDM sysems for daacommunicaion applicaions, IEEE Opical Inerconnecs Conference, Sana Fe, USA, MA2, May (212). 3. Z. Dong, J. Yu, H. C. Chien, N. Chi, L. Chen, and G. K. Chang, Ulra-dense WDM-PON delivering carriercenralized Nyquis-WDM uplink wih digial coheren deecion, Op. Express 19(12), (211). 4. M. F. Huang, D. Qian, and N. Cvijeic, A novel symmeric lighwave cenralized WDM-OFDM-PON archiecure wih OFDM-remodulaed ONUs and a coheren receiver OLT, European Conference and Exposiion on Opical Communicaions, Geneva, Swizerland, Tu.5.C, Sep. (211). 5. Y. Hsueh, M. F. Huang, S. Fan, and G. K. Chang, A novel lighwave cenralized bidirecional hybrid access nework: seamless inegraion of RoF wih WDM-OFDM-PON, IEEE Phoon. Technol. Le. 23(15), (211). 6. G.-H. Im, D. D. Harman, G. Huang, A. V. Mandzik, M.-H. Nguyen, and J.-J. Werner, Mb/s 16-CAP ATM LAN sandard, IEEE J. Sel. Areas Comm. 13(4), (1995). 7. R. Rodes, M. Wieckowski, T. T. Pham, J. B. Jensen, J. Turkiewicz, J. Siuzdak, and I. T. Monroy, Carrierless ampliude phase modulaion of VCSEL wih 4 bi/s/hz specral efficiency for use in WDM-PON, Op. Express 19(27), (211). 8. M. Wieckowski, J. B. Jensen, I. T. Monroy, J. Siuzdak, and J. P. Turkiewicz, 3 Mbps ransmission wih 4.6 bi/s/hz specral efficiency over 5 m PMMA POF link using RC-LED and muli-level carrierless ampliude phase modulaion, Op. Fiber Conf. (OFC 211), Los Angeles, USA, NTuB8., Mar. (211). 9. J. D. Ingham, R. V. Peny, and I. H. Whie, 4 Gb/s carrierless ampliude and phase modulaion for low-cos opical daacommunicaion links, Op. Fiber Conf. (OFC 211), Los Angeles, USA, OThZ3, Mar. (211). (C) 213 OSA 11 March 213 / Vol. 21, No. 5 / OPTICS EXPRESS 6459
2 1. X. Zhou and J. Yu, Muli-level, muli-dimensional coding for high-speed and high-specral-efficiency opical ransmission, J. Lighwave Technol. 27(16), (29). 11. J. Gao, Y. H. Leung, and V. Sreeram, Digial filers for carrierless ampliude and phase receivers, IEEE Inernaional Conference on Elecrical and Elecronic Technology, Singapore, no. 446, Augus (21). 12. J. Gao and Y. H. Leung, A new adapive equalizer for carrierless ampliude and phase (CAP) receivers, IEEE Inernaional Symposium on Circuis and Sysems, Orlando, USA, 3, 9 93, May (1999). 1. Inroducion A wide variey of daa and services drive he demand for higher capaciy opical communicaion sysems. To mee his demand, here have been significan amoun of research effor on improving he performance of an opical communicaion sysem. In long haul sysems, he effor has mainly been on increasing sysem specral efficiency and sysem reach. For he sysem of relaive shor disance, such as passive opical nework (PON) and shor reach opical communicaion sysem for daa cener inerconnecion, he effor has been more on finding he bes radeoff among cos, complexiy, daa rae and sensiiviy due o large amoun of ransceiver unis needed in such applicaions [1 5] and low-cos equipmen is a mus. A candidae echnique ha may provide good sysem performance using low cos opical componens such as direc modulaed laser (DML) and verical caviy surface emiing laser (VCSEL) is carrier-less ampliude and phase (CAP) modulaion. I allows relaively high daa rae o be achieved using opical componens of limied bandwidh. Comparing wih alernaive schemes such as quadraure ampliude modulaion (QAM) and orhogonal frequency division muliplexing (OFDM), no elecrical or opical complex-o-real-value conversion is necessary which involves a complex mixer and radio frequency (RF) source or opical IQ modulaor. Neiher does i require he discree Fourier ransform (DFT) ha uilized in OFDM signal generaion and demodulaion. The CAP signal can be generaed by using a digial filer wih several aps and a higher order modulaion can be realized, hus reducing he complexiy of compuaion and sysem srucure considerably. A number of opical communicaion sysems based on CAP have been demonsraed recenly [7 9]. In [7] and [8], sysems based on CAP16 and CAP64 are proposed bu he bi rae is only 1.25 Gb/s and 3 Mb/s respecively. References [2]. and [9] presen a CAP16 modulaion sysem wih bi rae up o 4 Gb/s. However, only limied resuls were presened wih no BER characerizaions. In addiion, since he channel response is no known in pracical siuaion, adapive equalizers are required. However, here is no deailed descripion abou he design of adapive equalizer and he digial filers. Their impac on sysem performance of opical CAP modulaion sysems was also no analyzed in previously published works. In his paper, we presen a deailed invesigaion on he design of digial filers and heir impac on sysem performance. An adapive equalizer based on cascaded muli-modulus algorihm (CMMA) [1] is presened and used for he demodulaion of CAP16 signal a he receiver. The impac of digial filer aps including shaping filers and mached filers on sysem performance is invesigaed hrough exensive simulaions and a 1 Gb/s CAP16 modulaion sysem is demonsraed experimenally. The BER performance for back-o-back (BTB) ransmission and over 2 km and 4 km fiber link is measured. 2. Operaing principle 2.1 Sysem srucure for CAP modulaion Figure 1 shows he schemaic diagram of sysem srucure based on CAP modulaion. For he CAP signal ransmier, he original bi sequence is firs fed o an encoder, which maps blocks of bis ino complex symbols and le T be he symbol period. The coded sequence is upsampled by a facor M, i.e. M-1 zeros is insered beween wo consecuive inpu symbols. Then he in-phase and quadraure componens of he up-sampling sequence are separaed and sen ino he digial shaping filer respecively. The oupus of he filers are subraced. The generaed CAP signal is passed hrough a digial-o-analog (D/A) converer and subsequenly performs opical up-conversion by driving an inensiy modulaor (IM) beween he minimum (C) 213 OSA 11 March 213 / Vol. 21, No. 5 / OPTICS EXPRESS 646
3 and maximum ransmission. Noe ha he digial shaping filers and D/A converer are operaing a a rae of M/T, bu he bandwidh of he opical modulaor is decided by he symbol rae of he sysem. A he receiver side, direc deecion is used and he received signal afer analog-o-digial (A/D) converer is fed ino wo differen mached filers o separae he in-phase and quadraure componens. The mached filers and A/D converer are also operaing a a rae of M/T. Afer down-sampling, an equalizer is employed for he complex signal and a decoder is uilized o obain he original bi sequence. Fig. 1. Schemaic diagram of sysem srucure based on CAP modulaion. 2.2 Theoreical foundaions for of CAP modulaion and demodulaion The generaed CAP signal can be expressed as ( ) ( ) ( ) ( ) ( ) s = a f b f (1) 1 2 where a ( ) and b( ) afer coding and up-sampling process respecively. The funcions f 1 ( ) and f 2 ( ) are he in-phase and quadraure componens of ransmied bi sequence are he corresponding shaping filers and form a so-called Hilber pair, as described in [6]. Noe ha he shaping filer should work a higher rae han he sysem symbol rae. So he up-sampling process here is used o mach he rae of shaping filer and o obain he oupu analog signal wihou he aliasing producs. If he square-roo raised-cosine funcion is employed as he baseband pulse response, he impulse responses of shaping filers are shown in Fig. 2(a). Assuming ha he channel response is ideal, he oupu of wo mached filers a he receiver is expressed as ri ( ) = s( ) m1( ) = ( a( ) f 1( ) b( ) f 2( ) ) m1( ) (2) r = s m = a f b f m q ( ) ( ) 2( ) ( ( ) 1( ) ( ) 2( )) 2( ) Here m1( ) = f 1( ) and m2( ) = f 2( ) are he impulse response of he corresponding mached filers [11,12] and denoes convoluion. Because he impulse response f 1 ( ) and f ( ) is even and odd funcions respecively [6], Eq. (2) can be simplified as 2 q ( ) = ( ) 1( ) = ( ) 11( ) ( ) 12( ) ( ) = ( ) ( ) = ( ) ( ) + ( ) ( ) ri s m a h b h r s m a h b h (3) (C) 213 OSA 11 March 213 / Vol. 21, No. 5 / OPTICS EXPRESS 6461
4 where h11 ( ) = f 1 ( ) f 1 ( ), h12 ( ) = f 1 ( ) f 2 ( ), h22 ( ) f 2 ( ) f 2 ( ) 2(d) indicaes he join impulse response h11 ( ), h12 ( ), 22 ( ) =. Figures 2(b)- h respecively. For he inphase componen in Eq. (3), he firs erm a he lef side is he desired signal componen. However, i is corruped by he second erm which comes from he quadraure componen. I h can be observed from he join impulse response h11 ( ) and h12 ( ) ha he maximum 11 ( ) coincides wih he zero of h12 ( ). Therefore, he desired in-phase componen can be exraced wihou iner-symbol inerference (ISI) and he disorion ha comes from he quadraure componens a an appropriae sample ime. The same conclusion can be obained for he quadraure componen in Eq. (3). Because of he serious ISI, synchronizaion is very imporan in CAP demodulaion. However, he appropriae sampling ime is hard o decide and sampling ime offses will lead o subsequen signals seriously affeced by ISI and he crossalk beween he in-phase and quadraure componens. Considering ha he disorions induced by eiher he ISI or crossalk is linear, an equalizer is needed o recover he oupu signal of mached filers. The classic CMA [1] becomes popular because i is a blind algorihm and easy o realize. However, i is much less effecive for muli-level signal modulaion sysem, as he symbols in our sysem do no have consan ampliude and he error funcion in he adapaion process will no approach zero even for an ideal muli-level signal wihou disorion. Therefore, he cascaded mulimodulus algorihm (CMMA) wih modified error funcion is used for he muli-level CAP signal [1] sudied in his paper. I is modified slighly for he muli-level CAP sysem as here is only one complex inpu for he equalizer as supposed o polarizaion-muliplexed (PM) ransmission in long-haul sysems. Therefore, he synchronizaion process can be considered o be implicily done hrough he blind adapive CMMA. 1. (a) In-phase Quadraure 1. (b) h11 () (c) h12 () 1. h22 () - - (d) Fig. 2. The impulse responses of (a) in-phase and quadraure shaping filers, (b) h11 ( ), (c) h12 ( ), (d) h22 ( ). 3. Simulaion resuls The sysem described in he previous secion is invesigaed hrough VPI Transmission Maker simulaion. The original bi sequence is mapped ino 4 levels and he symbol rae is se a 1 Gbaud. The compuaional complexiy o generae and demodulae CAP signals is direcly relaed wih he number of aps of he shaping and mached filers. Therefore, i is imporan o invesigae he requiremens of he CAP filer in order o reduce he compuaional complexiy while mainaining a good performance. (C) 213 OSA 11 March 213 / Vol. 21, No. 5 / OPTICS EXPRESS 6462
5 Considering he relaions beween up-sampling facor and he required number of filer aps, we sudy a parameer ε defined as he raio beween he number of aps of shaping or mached filers and he up-sampling facor. The parameer ε can be also considered as he number of symbols ha conribue o he ISI. The frequency response of he filers wih differen ε is shown in Fig. 3(a), and he impac of differen number of aps of he shaping filers and mached filers on he sysem performance is shown in Fig. 3(b) a a received power of 22 dbm. I is observed ha he BER decreases wih he increasing ε of mached filers a he receiver for differen ε of shaping filers a he ransmier, because he main lobe of he frequency response of he mached filers is narrower and he side lobe decreases faser wih larger ε as shown in Fig. 3(a), hereby he inband OSNR afer mached filer increases wih larger ε, which leads o beer BER performance. When ε exceeds 4, he frequency responses of mached filers are almos he same, and so he BER almos remains unchanged. I can be also found ha BER performance degrades wih increasing ε. This is because he induced ISI is more serious when ε is larger. Alhough he CMMA-based equalizer can compensae his linear disorion, he equalizer performance degrades in he presence of noise. In order o make a furher illusraion, he BER performance of back-o-back (BTB) ransmission wih differen ε is presened in Fig. 3(c). The BER curve a ε = 2 performs beer han ohers. I is also found ha he BER performance are closer wih each oher when he received opical power is increasing, suggesing ha he OSNR of received signal has an influence on he olerance of he equalizer o ISI. However, i does no mean ha ε should be reduced. Figure 3(d) shows he power penaly a BER of 1 3 induced by chromaic dispersion (CD) for differen values of ε. I shows ha larger ε will improve he sysem performance. There is no inline dispersion compensaion, so he bandwidh of generaed CAP signal, which depends on ε, will affec he BER performance. In conclusion, he parameer ε of shaping and mached filers will impac he BER performance of he ransmission link. An appropriae value of ε should be chosen based on he requiremen of compuaional complexiy and ransmission disance. Power (dbm) (a) ε = 2 ε = 4 ε = 6 ε = 8 BER 1 1E-3 (b) ε of shaping filer = 2 ε of shaping filer = 4 ε of shaping filer = 6 ε of shaping filer = 8 BER -3 1E Frequency (GHz) 8 (c) ε of shaping filer = 2 (d) 1 ε of shaping filer = 4 7 ε of shaping filer = 6 ε of shaping filer = 8 6 1E-3 1E-4 1E Received opical power (dbm) Power penaly a BER of ε of mached filer ε of shaping filer = 2 ε of shaping filer = 4 ε of shaping filer = 6 ε of shaping filer = Dispersion (ps/nm) Fig. 3. (a) Frequency response of shaping or mached filers wih differen ε, (b) BER performance wih differen ε a received power of 22 dbm, (c) BER versus received opical power wih differen ε when ε equals 8, (d) Dispersion-induced power penaly for differen ε. (C) 213 OSA 11 March 213 / Vol. 21, No. 5 / OPTICS EXPRESS 6463
6 4. Experimenal seup and resuls The experimenal seup of CAP16 ransmission sysem is shown in Fig. 4. Firsly, he CAP16 signal is generaed offline by MATLAB and he original daa sequence is mapped ino 4 levels and M-1 zeros are insered beween wo consecuive inpu symbols, making he original mapping daa up-sampled by a facor of 4 [7]. Afer I/Q separaion, he wo branches of daa sequences is sen ino wo shaping filers wih 32 aps. An arbirary waveform generaor (AWG) is used o produce he RF signal a 1 GSa/s so ha he symbol rae 1/T of he CAP16 signal is 2.5 Gbaud. I should be noed ha he symbol rae is limied by he bandwidh of he AWG used in our experimen, because here is power aenuaion a higher frequency componen. Some pre-emphasis echniques can be adoped o furher increase he sysem s symbol rae. The square-roo raised-cosine funcion is used as he baseband impulse response and is roll-off coefficien is se o.1. The excess bandwidh is se o 4%. A CW laser a nm from exernal caviy laser wih a linewidh less han 1 khz is used as he signal source. Then oupu RF signal is subsequenly used o drive he inensiy modulaor (IM) beween he minimum and maximum ransmission. The fiber launch power is se a 2.8 dbm. Afer fiber ransmission, he CAP16 signal is deeced by a phoodiode (PD) wih a responsiviy of.65 A/W and sampled by an oscilloscope a a sampling rae of 1 GSa/s and processed off-line by MATLAB. Figure 5(a) shows he elecrical specrum of he received CAP16 signal. For he offline processing, he sampled signal is sen ino wo mached filers wih 32 aps, so he in-phase and quadraure signals are separaed and followed by a downsampling process, because he CMMA algorihm operaes a a rae of 2/T. Finally, he carrier phase recovery is employed based on he convenional 4h power Vierbi-Vierbi phase esimaion algorihm. The capured and processed CAP16 bis for bi error couning are over 2 x 1 5. We hen measured he BER performance of he CAP16 sysem wih BTB and over differen ransmission lengh and he resuls are shown in Fig. 5(b). I is found ha he required received power a BER of 1 3 for BTB ransmission is 24.9 dbm. Because here is no inline and offline dispersion compensaion in his CAP16 sysem, here is receiver power penaly afer fiber ransmission. 2 db and 3.5 db receiver power penaly are observed a BER of 1 3 wih 2 km and 4 km fiber link respecively. The recovered consellaions a received power of 22.8 dbm wih or wihou fiber link are also shown in Fig. 5(b), clearly demonsraing he feasibiliy of he proposed CAP16 ransmission sysem. 4-levels Demapping 4-levels Mapping Carrier recovery CMMA I/Q Seperaion Upsampling Downsampling I/Q Shaping filer I/Q Combinaion I/Q Subracion I/Q mached filer Fig. 4. Experimen seup of 1 Gb/s CAP16 modulaion sysem. ECL: exernal caviy laser, IM: inensiy modulaor, AWG: arbirary waveform generaor. (C) 213 OSA 11 March 213 / Vol. 21, No. 5 / OPTICS EXPRESS 6464
7 A Elecrical power (db) 4 B C 1 2 BER C B 1E-3-2 A 1E Frequency (GHz) (a) BTB Afer 2 km Afer 4 km Received opical power(dbm) (b) Fig. 5. (a) Elecrical specrum of received CAP16 signal, (b) BER performance versus received opical power wih differen ransmission lenghs. 4. Conclusions In his paper, a deailed invesigaion on he digial filers in CAP modulaion sysems was presened hrough comprehensive simulaions. An adapive equalizer based on cascaded muli-modulus algorihm (CMMA) is used for he demodulaion a he receiver and he impac of digial filer aps on sysem performance is invesigaed. I can be concluded ha he shaping and mached filer aps will have considerable influence on he BER performance of he ransmission sysem. The appropriae number of digial filer aps will be chosen based on compuaional complexiy and ransmission disance consideraions. In addiion, a 1 Gb/s CAP16 modulaion sysem is demonsraed experimenally and he BER performance for differen ransmission disances are obained. Compared wih back-o-back ransmission, 2 db and 3.5 db receiver power penalies are observed a BER of 1 3 wih ransmission disance of 2 km and 4 km respecively. I clearly demonsraes he feasibiliy of using CAP16 modulaion for fuure shor range ransmission sysems. Acknowledgmens This work was parially suppored by he NHTRDP (973) of China (Gran No. 21CB3283), NNSF of China (No , No ), NHTRDP (863 Program) of China (211AA132, 212AA1132), The Naional Key Technology R&D Program (212BAH18B) and G-UA44 of The Hong Kong Polyechnic Universiy. # $15. USD (C) 213 OSA Received 18 Jan 213; revised 22 Feb 213; acceped 22 Feb 213; published 7 Mar March 213 / Vol. 21, No. 5 / OPTICS EXPRESS 6465
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